Wireless communication apparatus and frequency hopping method

ABSTRACT

Disclosed are a wireless communication apparatus and frequency hopping method which minimize the change in the instantaneous power distribution characteristics of the time waveform of transmission signals when a plurality of channels are multiplexed by frequency division. At a terminal ( 200 ), a mapping unit ( 212 ) maps the PUCCH to frequency resources of a first slot, maps the PUSCH to frequency resources, among the frequency resources of the first slot, separated exactly by predetermined frequency spacing (B) from the frequency resources to which the PUCCH is mapped, and cyclically shifts the frequencies so as to map the PUCCH and PUSCH to frequency resources, within an IDFT or IFFT bandwidth, of a second slot while maintaining the predetermined frequency spacing (B), thereby allowing frequency hopping of the PUCCH and PUSCH between the first slot and the second slot.

TECHNICAL FIELD

The present invention relates to a radio communication apparatus and afrequency hopping method for frequency division multiplexing andtransmitting a plurality of channels.

BACKGROUND ART

3GPP (Generation Partnership Project) is studying standardization ofLTE-advanced as a mobile communication system which becomes a successorof LTE (Long Term Evolution). LTE-advanced has decided to adoptDFT-spread OFDM (DFT-S-OFDM) using DFT (Discrete Fourier Transform)precoding which is also adopted in LTE as an uplink (UL) radio accessscheme or SC-FDMA (Single-Carrier Frequency Division Multiple Access).

In LTE UL transmission using SC-FDMA, the following method is adopted asa frequency resource allocation and mapping method of UL physicalchannel (physical uplink shared channel (PUSCH), physical uplink controlchannel (PUCCH)) that transmits a data signal and control signal toimprove transmission quality while maintaining low PAPR (Peak-to-AveragePower Ratio) characteristics of a transmission signal capable ofrealizing high coverage.

[Regarding PUSCH]

A DFT-spread data signal (or control signal or signal resulting frommultiplexing a data signal and control signal) of each terminalapparatus (User Equipment, hereinafter abbreviated as “terminal” or“UE”) is mapped to a continuous frequency band of a PUSCH region in alocalized manner.

In addition, a resource allocation method is also available whereby asignal mapped to a continuous frequency band of a PUSCH region issubjected to frequency hopping (inter-slot frequency hopping) betweentwo slots; first-half slot and second-half slot, configured by dividingone subframe into two portions in the PUSCH region.

[Regarding PUCCH]

A control signal spread using a CAZAC (Constant Amplitude ZeroAutocorrelation) sequence is subjected to frequency hopping (inter-slotfrequency hopping) between two slots; first-half slot and second-halfslot, configured by dividing one subframe into two portions in the PUCCHregion.

[Regarding PUCCH and PUSCH]

Each terminal does not simultaneously transmit PUSCH for mapping a datasignal or the like and PUCCH for mapping a control signal. That is, thePUSCH and PUCCH are not frequency-multiplexed and transmitted.Therefore, a method is adopted whereby when a control signal and datasignal are generated simultaneously, both signals are multiplexed intoone signal sequence, DFT-spread and mapped to a continuous frequencyband of a PUSCH region.

As described above, the frequency resource allocation and mapping methodin an LTE UL physical channel (1) maps a signal to a continuousfrequency band in a localized manner to thereby maintain a low PAPRcharacteristic of a UL SC-FDMA signal and (2) use inter-slot frequencyhopping, and can thereby improve a frequency diversity effect and aneffect of suppressing other cell interference.

For example, Patent Literature 1 discloses an inter-slot frequencyhopping method for an uplink physical channel (uplink control channel,uplink shared channel or the like) targeted at a UL SC-FDMA scheme inLTE.

However, due to the influence of limitations to the above-describedPUSCH and PUCCH frequency resource allocation and mapping method, thereis a problem that flexibility of UL frequency resource allocation islow, and therefore the following method is under study aboutLTE-advanced UL SC-FDMA transmission (see Non-Patent Literature 1 andNon-Patent Literature 2).

[Regarding PUCCH and PUSCH]

A method of simultaneously transmitting PUSCH for mapping a data signalor the like and PUCCH for mapping a control signal (e.g. L1/L2 controlsignal). That is, a method of transmitting PUSCH and PUCCH for eachterminal through frequency division multiplexing.

FIG. 1 shows an example of time-frequency resource mapping of PUCCH andPUSCH within one subframe by a terminal that frequency divisionmultiplexes and transmits the PUSCH and PUCCH. The PUCCH to which acontrol signal is mapped frequency-hops at both edges of a system bandsubjected between slots. On the other hand, the PUSCH to which a datasignal or the like is mapped is allocated to continuous resources in thefrequency direction and time direction within one subframe in a PUSCHregion sandwiched between PUCCH regions, thereby realizing simultaneoustransmission of the PUSCH and PUCCH.

When a control signal and data signal are generated simultaneously, thismakes it possible to avoid the following problems in the mapping methodthrough an LTE UL physical channel, that is, the method of multiplexingboth signals, applying DFT spreading to the signal sequence generatedand then mapping the signal sequence to a continuous frequency band ofthe PUSCH.

That is, when a control signal and data signal are generatedsimultaneously, the signals are multiplexed and mapped to the PUSCHregion, and it is thereby possible to solve the problems that (1) thecontrol signal is not mapped to the allocated PUCCH and therefore theresource utilization efficiency of the PUCCH deteriorates and that (2)the amount of data that can be transmitted with frequency resources ofthe PUSCH is reduced and the data throughput deteriorates.

CITATION LIST Patent Literature PTL 1

-   Japanese Patent Application Laid-Open No. 2009-49541

Non-Patent Literature NPL 1

-   3GPP TR 36.814 v.1.0.0, “Further Advancements for E-UTRA Physical    Layer Aspects,” March, 2009

NPL 2

-   R1-090611, “Concurrent PUSCH and PUCCH transmissions,” 3GPP RAN WG1    #56, February, 2009

NPL 3

-   3GPP TS 36.211 v.8.9.0, “Physical Channels and Modulation (Release    8),” December, 2009

SUMMARY OF INVENTION Technical Problem

However, when the above-described prior art is used, the frequencymapping position of the PUCCH changes between slots within one subframe(one TTI (Transmission Time Interval)), and therefore the instantaneouspower distribution characteristic (e.g. PAPR complementary cumulativedistribution function (CCDF) characteristic) of the transmission signalwaveform in the time domain changes between slots. This results in aproblem that the distortion characteristic of the transmission signalcaused by nonlinearity of input/output characteristics of a poweramplifier (PA) changes between the first-half slot and second-half slot.

Hereinafter, the above-described problems will be described in furtherdetail.

To improve power efficiency of the PA while avoiding distortion of thetransmission signal caused by non-linearity of the input/outputcharacteristics of the PA, it is generally preferable to cause the PA tooperate in the vicinity of a certain value (operation point) at which amargin is provided according to an instantaneous power variation widthof the transmission signal waveform from a change point of thelinear-non-linear region of the input/output characteristics of the PA(see FIG. 2). However, when the above prior art is used, the mappingposition of the PUCCH in the frequency domain differs between thefirst-half slot and the second-half slot, and therefore as shown in FIG.2, there may be a case where the instantaneous power variation width ofthe time waveform of the transmission signal in the second-half slot(slot #1) is greater than the instantaneous power variation width of thetime waveform of the transmission signal in the first-half slot (slot#0) (e.g. the value of PAPR at which a CCDF of PAPR becomes 1% (=10-2)).As a result, the distortion characteristic of a transmission SC-FDMAsignal changes between the first-half slot and the second-half slot. Forexample, as shown in FIG. 2, when the instantaneous power variationwidth of the first-half slot is small and the instantaneous powervariation width of the second-half slot is large, distortion of thetransmission SC-FDMA signal in the second-half slot is greater thandistortion of the transmission SC-FDMA signal in the first-half slot.

As described above, when AMC (Adaptive Modulation and Coding) control ortransmission power control is operated so as to satisfy certain requiredquality using the same transmission format (e.g. same MCS (Modulationand channel Coding Scheme) set or a certain transmission power controlvalue instructed by a base station apparatus (hereinafter abbreviated as“base station”) using a transmission power command or the like withinone subframe (one TTI), there is a problem that the receiving qualitydeteriorates caused by the distortion characteristic of the SC-FDMAsignal in the second-half slot and the required quality cannot besatisfied and a data signal of the one entire subframe comprised of twoslots cannot be received correctly. LTE controls the transmission format(MCS set or transmission power control value) of the one entire subframecomprised of two slots of UL under the instruction of the downlinkcontrol channel (PDCCH: Physical Downlink Control Channel) reported ineach subframe of the downlink (DL). For this reason, if the terminalchanges the MCS set for each slot by taking into account the change ofthe distortion characteristic of the SC-FDMA signal between slots, thebase station may not be able to correctly recognize the transmissionformat for each slot of the UL and may not be able to correctly receivethe data signal of the one entire subframe. When the data signal of theone entire subframe cannot be received correctly, retransmission takesplace, leading to a problem of a delay or the like.

Furthermore, when pre-distortion for compensating non-linear distortionof the PA is used together with the PA, if the distortion characteristicof the SC-FDMA changes between the first-half slot and the second-halfslot, there is also a problem that optimum control of the pre-distortionin the first-half slot will not work out in the second-half slot.

It is therefore an object of the present invention to provide a radiocommunication apparatus and a frequency hopping method when a pluralityof channels are frequency division multiplexed, capable of suppressingchanges in an instantaneous power distribution characteristic of a timewaveform of a transmission signal.

Solution to Problem

A radio communication apparatus according to the present inventionadopts a configuration including an arrangement section that arranges asignal of a first channel to frequency resources of a first slot and asecond slot transmitted in a predetermined transmission format andarranges a signal of a second channel to frequency resources located apredetermined frequency interval apart from a frequency resource of thefrequency resources of the first slot in which the first channel isarranged, and an inverse Fourier transform section that applies inversediscrete Fourier transform (IDFT) or inverse fast Fourier transform(IFFT) to the signals arranged in the first channel and the secondchannel, wherein the arrangement section cyclically frequency shiftswithin an IDFT or IFFT bandwidth while maintaining the predeterminedfrequency interval, arranges the signals of the first channel and thesecond channel to frequency resources of the second slot and therebycauses the first channel and the second channel to perform frequencyhopping between the first slot and the second slot.

A frequency hopping method of the present invention includes anarranging step of arranging a signal of a first channel to frequencyresources of a first slot and a second slot transmitted in apredetermined transmission format and arranging a signal of a secondchannel in a frequency resource located a predetermined frequencyinterval apart from a frequency resource of the frequency resources ofthe first slot in which the first channel is arranged, and atransforming step of applying inverse discrete Fourier transform (IDFT)or inverse fast Fourier transform (IFFT) to the signals arranged in thefirst channel and the second channel, wherein in the arranging step, thesignals of the first channel and the second channel are cyclicallyfrequency shifted within an IDFT or IFFT bandwidth while maintaining thepredetermined frequency interval, arranged to frequency resources of thesecond slot, and the signals of the first channel and the second channelare thereby caused to perform frequency hopping between the first slotand the second slot.

Advantageous Effects of Invention

The present invention frequency division multiplexes and transmits aplurality of channels, and can thereby suppress changes in aninstantaneous power distribution characteristic of a time waveform of atransmission signal in a predetermined time segment in which the signalis transmitted in a predetermined transmission format (MCS set ortransmission power control value) while suppressing the deterioration ofthe frequency utilization efficiency and throughput.

BRIEF DESCRIPTION OF DRAWINGS

FIG. 1 is a diagram illustrating simultaneous transmission (frequencydivision multiplexing transmission) of PUCCH and PUSCH;

FIG. 2 is a diagram illustrating a situation in which the instantaneouspower variation width of a time waveform of a transmission signalchanges between slots;

FIG. 3 is a block diagram illustrating main components of a base stationaccording to Embodiment 1 of the present invention;

FIG. 4 is a block diagram illustrating main components of a terminalaccording to Embodiment 1;

FIG. 5 is a diagram illustrating an example of [inter-slot hoppingpattern #1];

FIG. 6 is a diagram illustrating a definition of frequency interval;

FIG. 7 is a diagram illustrating an example of an inter-slot hoppingpattern when the number of frequency division multiplexed channels is 3or more;

FIG. 8 is a diagram illustrating an example of frequency divisionmultiplexed signals having different statistical properties;

FIG. 9 is a sequence diagram illustrating an example of a controlprocedure when performing inter-slot frequency hopping;

FIG. 10 is a sequence diagram illustrating an example of a controlprocedure when performing inter-slot frequency hopping;

FIG. 11 is a sequence diagram illustrating another example of thecontrol procedure when performing inter-slot frequency hopping;

FIG. 12 is a sequence diagram illustrating a further example of thecontrol procedure when performing inter-slot frequency hopping;

FIG. 13 is a sequence diagram illustrating a method of reporting anamount of cyclic frequency shift;

FIG. 14 is a sequence diagram illustrating a method of reporting anamount of cyclic frequency shift;

FIG. 15 is a diagram illustrating an example of [inter-slot hoppingpattern #2] (frequency division multiplexing of PUCCHs (2 PUCCHs) percomponent band);

FIG. 16 is a diagram illustrating another example of [inter-slot hoppingpattern #2] (frequency division multiplexing of PUSCHs (two PUSCHs) percomponent band);

FIG. 17 is a diagram illustrating a further example of [inter-slothopping pattern #2] (when PUCCH performs inter-slot frequency hoppingbetween different component bands);

FIG. 18 is a diagram illustrating an example of [inter-slot hoppingpattern #3];

FIG. 19 is a diagram illustrating an example of [inter-slot hoppingpattern #4];

FIG. 20 is a diagram illustrating an example of [inter-slot hoppingpattern #5];

FIG. 21 is a diagram illustrating an example of [inter-slot hoppingpattern #6];

FIG. 22 is a diagram illustrating an example of [inter-slot hoppingpattern #8];

FIG. 23 is a diagram illustrating another configuration of the terminalaccording to Embodiment 1;

FIG. 24 is a diagram illustrating an example of an inter-slot frequencyhopping pattern when a plurality of channels are mapped to continuousfrequency resources;

FIG. 25 is a diagram illustrating an example of [frequency intervalsetting method #1-0];

FIG. 26 is a diagram illustrating a table of correspondence between thefrequency distances from both edges of the system band and the centralfrequency of the system band, frequency interval B and maximum value(threshold) of frequency interval B based on [frequency interval settingmethod #1-1];

FIG. 27 is a diagram illustrating an example of [frequency intervalsetting method #1-2];

FIG. 28 is a diagram illustrating a table of correspondence between thefrequency distance from both edges of the system band, frequencyinterval B (or maximum value of frequency interval B) based on[frequency interval setting method #1-2];

FIG. 29 is a diagram illustrating an example of [frequency intervalsetting method #1-3];

FIG. 30 is a diagram illustrating a table of correspondence between thefrequency distance from both edges of the system band, totaltransmission power of a frequency division multiplexed signal, frequencyinterval B (maximum value of frequency interval B) based on [frequencyinterval setting method #1-3];

FIG. 31 is a diagram illustrating a table of correspondence between thefrequency distance from both edges of the system band, transmissionpower of one channel of a plurality of channels making up a frequencydivision multiplexed signal, frequency interval B (maximum value offrequency interval B) based on [frequency interval setting method #1-3];

FIG. 32 is a diagram illustrating a correlation between resource numberm of a frequency resource in which PUCCH is arranged and the position ofa physical channel resource;

FIG. 33 is a diagram illustrating an example of [inter-slot hoppingpattern #9];

FIG. 34 is a diagram illustrating another example of [inter-slot hoppingpattern #9];

FIG. 35 is a diagram illustrating an example of inter-slot hoppingpattern to be compared;

FIG. 36 is a diagram illustrating an example of [inter-slot hoppingpattern #10];

FIG. 37 is a diagram illustrating another example of [inter-slot hoppingpattern #10];

FIG. 38 is a diagram illustrating a correction term and an amount ofcyclic frequency shift within a hopping band according to Embodiment 4of the present invention;

FIG. 39 is a diagram illustrating an example of [inter-slot hoppingpattern #11];

FIG. 40 is a diagram illustrating an example [inter-slot hopping pattern#12];

FIG. 41 is a diagram illustrating an example of [inter-slot hoppingpattern #13];

FIG. 42 is a flowchart for realizing inter-slot frequency hopping basedon [inter-slot hopping pattern #13];

FIG. 43 is a diagram illustrating an example of [inter-slot hoppingpattern #14]; and

FIG. 44 is a diagram illustrating an example of [inter-slot hoppingpattern #15].

DESCRIPTION OF EMBODIMENTS

Hereinafter, embodiments of the present invention will be described indetail with reference to the accompanying drawings.

The present inventors have arrived at the present invention bydiscovering that, when a plurality of channels such as PUCCH and PUSCHare frequency division multiplexed and caused to perform inter-slotfrequency hopping, if the influence of the frequency hopping method on achange of the time waveform (combined time waveform of the plurality ofchannels) of the signal after the frequency division multiplexing can belimited to only phase components, the instantaneous power distributioncharacteristic (e.g. CCDF characteristic of PAPR) of the time waveformof a transmission signal does not change between slots.

In the following descriptions, regarding two slots configured bydividing one subframe into two portions, the first-half slot is called“first slot” and the second-half slot is called “second slot.”

Embodiment 1

When the frequency interval between a first channel and a second channelallocated to the first slot in an IDFT (Inverse Discrete FourierTransform) or IFFT (Inverse Fast Fourier Transform) band is B, thepresent embodiment cyclically allocates the second channel to afrequency resource in the second slot located B apart from the firstchannel within the IDFT or IFFT bandwidth.

Here, the IDFT or IFFT band may be called “system (component band)band.” In an LTE-A system, to simultaneously realize communication at anultra-high speed several times the transmission rate in the LTE systemand backward compatibility for the LTE system, the band for the LTE-Asystem is divided into “component bands” of 20 MHz or below, which is abandwidth support by the LTE system. That is, the “component band” is aband having, for example, a width of maximum 20 MHz and defined as abase unit of a communication band. Furthermore, the “component band” mayalso be expressed as “component carrier(s)” in English in 3GPPLTE-Advanced.

FIG. 3 shows main components of a base station that receives uplink dataaccording to the present embodiment. To avoid explanations from becomingcomplicated, FIG. 3 shows components related to reception of uplink dataclosely related to the present invention and transmission over adownlink of a response signal to uplink data, and omits illustrationsand descriptions of components related to transmission of downlink data.

Base station 100 is comprised of transmitting/receiving antenna port101, radio reception processing section 102, SC-FDMA signal demodulationsection 103, demodulation section 104, channel decoding section 105,quality measuring section 106, frequency hopping control section 107,scheduling section 108, control information generation section 109,channel coding sections 110-1 and 110-2, modulation sections 111-1 and111-2, OFDM signal modulation section 112 and radio transmissionprocessing section 113.

Radio reception processing section 102 converts, to a baseband signal, aUL SC-FDMA signal resulting from frequency division multiplexing aplurality of channels (PUSCH, PUCCH or the like) transmitted from aterminal on the transmitting side that transmits uplink data received bytransmitting/receiving antenna port 101. Here, the UL SC-FDMA signal isa multi-carrier (MC) signal resulting from frequency divisionmultiplexing a plurality of different channels as will be describedlater and is a signal having a greater PAPR than a single carrier FDMAsignal in LTE. Therefore, there is some difference in the meaning of theterm between the UL SC-FDMA signal according to the present embodimentand single carrier FDMA signal of LTE featuring a low PAPR, but forsimplicity of explanation, a signal in which a plurality of channels arefrequency-multiplexed will be called “SC-FDMA signal” and describedhereinafter.

SC-FDMA signal demodulation section 103 is internally provided with a CP(Cyclic Prefix) removing section, an FFT (Fast Fourier Transform)section, a demapping section, an FDE (Frequency Domain Equalization)section and an IDFT section, and performs the following processing. TheCP removing section removes a CP added at the head of the SC-FDMA signaland inputs the SC-FDMA signal after the CP removal to the FFT section.The FFT section applies FFT to the SC-FDMA signal after the CP removal,thereby transforms the SC-FDMA signal from a time domain to a frequencydomain subcarrier component (orthogonal frequency component), andoutputs the subcarrier component after the FFT to the demapping section.When the subcarrier component after the FFT is a reference signal, theFFT section outputs the subcarrier component to quality measuringsection 106. The demapping section demaps the data and control signalmapped to each subcarrier (orthogonal frequency component) of frequencyresources used by a target terminal based on resource allocationinformation (which will be described later) of each terminal inputtedfrom scheduling section 108 and outputs the demapped data and signal tothe FDE section. The FDE section calculates an FDE weight from anestimate value of a frequency channel gain between each terminal and thebase station, equalizes the received data and control signal in thefrequency domain and outputs the data signal to IDFT section and outputsthe control signal to the despreading section. The IDFT section appliesIDFT to the data signal in the frequency domain after the FDE,transforms the data signal into a time domain data signal and outputsthe time domain data signal to demodulation section 104. The despreadingsection performs despreading processing on the control signal after theFDE and outputs the control signal to demodulation section 104.

Demodulation section 104 performs demodulation such as QPSK modulationor the like on the equalized received data and control signal based onMCS information inputted from scheduling section 108 and outputs thedemodulated data and control signal to channel decoding section 105.

Channel decoding section 105 performs decoding processing such as turbodecoding (Viterbi decoding) on the demodulated data and control signalbased on the MCS information inputted from scheduling section 108 andthen reconstructs the data and control signal. Furthermore, channeldecoding section 105 outputs resource allocation request information ofPUSCH and PUCCH included in the reconstructed control signal tofrequency hopping control section 107 and scheduling section 108.

Quality measuring section 106 measures channel quality of each terminalin the frequency domain, for example, an SINR (Signal-to-Interferenceplus Noise power Ratio) for each subcarrier of each terminal usingreference signals of all terminals extracted from subcarrier componentsafter FFT and outputs the channel quality as CQI (Channel QualityIndicator or Channel Quality Information) to frequency hopping controlsection 107 and scheduling section 108.

Frequency hopping control section 107 receives CQI of each terminal,traffic type and resource allocation request information of PUSCH andPUCCH as input and decides whether or not to perform inter-slotfrequency hopping. For example, when resource allocation requests forPUSCH and PUCCH (or a plurality of PUSCHs, or a plurality of PUCCHs) aresimultaneously generated, frequency hopping control section 107 decidesto apply inter-slot frequency hopping. Frequency hopping control section107 reports indication information (frequency hopping indicationinformation) indicating the presence or absence of indication as towhether or not to apply inter-slot frequency hopping to a targetterminal to scheduling section 108 and control information generationsection 109. Furthermore, when frequency hopping is applied, frequencyhopping control section 107 reports information of the amount of cyclicfrequency shift to control information generation section 109.

A case has been described above where base station 100 decides whetheror not to apply inter-slot frequency hopping to the terminal based onthe presence or absence of resource allocation request information forPUSCH and PUCCH from the terminal, but base station 100 may also decidewhether or not to apply inter-slot frequency hopping based on the reportinformation such as PHR (Power Head Room) from the terminal or a movingspeed or the like of the terminal.

Scheduling section 108 outputs the information of MCS (modulationscheme, coding rate or the like) determined based on CQI to controlinformation generation section 109, SC-FDMA signal demodulation section103, demodulation section 104 and channel decoding section 105.

Furthermore, scheduling section 108 performs two-dimensional schedulingof time and frequency based on inputted QoS (request data rate, requirederror rate, delay or the like) of each terminal, resource allocationrequest information for CQI, PUSCH and PUCCH and frequency hoppingindication information, and thereby allocates time and frequencyresources to PUSCH and PUCCH. Scheduling section 108 outputs informationof resources (time, frequency) allocated to PUSCH and PUCCH (resourceallocation information) to control information generation section 109and SC-FDMA signal demodulation section 103.

Control information generation section 109 converts control informationsuch as inputted MCS information of the terminal, resource allocationinformation of PUSCH and PUCCH, frequency hopping indication informationand amount of cyclic frequency shift of inter-slot frequency hopping orthe like to a binary control bit sequence to be reported to the terminaland outputs the control bit sequence after the conversion to channelcoding section 110-1.

Channel coding section 110-1 applies error correcting coding such asconvolutional coding to the control bit sequence at a predeterminedcoding rate and then outputs the coded bit sequence to modulationsection 111-1.

Channel coding section 110-2 applies error correcting coding such asturbo coding to the transmission data sequence at a predetermined codingrate and then outputs the coded bit sequence to modulation section111-2.

Modulation sections 111-1 and 111-2 modulate the coded bit sequenceusing QPSK or the like and outputs the control and data symbol sequenceobtained to OFDM signal modulation section 112.

OFDM signal modulation section 112 is internally provided with an S/Psection, a mapping section, an IFFT section, a P/S section and a CPinsertion section, and multiplexes the inputted control and data symbolsequence and then applies processing such as serial/parallel conversion(S/P conversion), mapping to subcarriers, IFFT (Inverse Fast FourierTransform), parallel/serial conversion (P/S conversion), CP insertionand outputs the processed sequence to radio transmission processingsection 113.

Radio transmission processing section 113 converts a baseband signal toan RF (Radio Frequency) signal, amplifies power thereof by a poweramplifier (PA) and transmits the signal to transmitting/receivingantenna port 101.

FIG. 4 shows main components of the terminal according to the presentembodiment. To avoid the explanation from becoming complicated, FIG. 4shows components related to transmission of uplink data closely relatedto the present invention and reception of a response signal on thedownlink for the uplink data and omits illustrations and descriptions ofcomponents related to downlink data.

Terminal 200 is provided with transmitting/receiving antenna port 201,radio reception processing section 202, OFDM signal demodulation section203, demodulation section 204, channel decoding section 205, controlinformation extraction section 206, control section 207, channel codingsections 208-1 and 208-2, modulation sections 209-1 and 209-2, DFTsection 210, spreading section 211, mapping section 212, IFFT section213, CP insertion section 214 and radio transmission processing section215.

Radio reception processing section 202 converts a signal transmittedfrom base station 100 and received by transmitting/receiving antennaport 201 to a baseband signal.

OFDM signal demodulation section 203 applies CP removal, S/P conversion,FFT, FDE processing, demapping, P/S conversion processing to thebaseband signal and then outputs a control and data symbol sequence todemodulation section 204.

Demodulation section 204 applies demodulation processing such as QPSKmodulation to the control and data signal sequence and outputs thedemodulated control and data sequence to channel decoding section 205.

Channel decoding section 205 applies error correcting decoding to thedemodulated control and data sequence using turbo decoding or the likeand reconstructs the control and data signal.

Control information extraction section 206 extracts resource allocationinformation of PUSCH and PUCCH of terminal 200, frequency hoppingindication information and the amount of cyclic frequency shift ofinter-slot frequency hopping (hereinafter referred to as “inter-slotfrequency hopping information”) from among the reconstructed control anddata signal and outputs the extracted inter-slot frequency hoppinginformation to control section 207. Furthermore, control informationextraction section 206 outputs control information of MCS informationother than the inter-slot frequency hopping information (modulationlevel (M-ary modulation value), coding rate or the like) to channelcoding sections 208-1 and 208-2 and modulation sections 209-1 and 209-2.

Control section 207 sets time and frequency resources to be mapped bycausing PUSCH and PUCCH to hop between slots in a first and second slotswithin a subframe using inputted inter-slot frequency hoppinginformation of the terminal directed to the terminal and outputsinformation (hereinafter referred to as “resource mapping information”)of the set time and frequency resources (resource mapping) to mappingsection 212.

Channel coding section 208-1 for transmission data applies errorcorrecting coding such as turbo coding to an information bit sequence(transport block, codeword) of the transmission data inputted from ahigher layer, generates a coded bit sequence with a certain coding ratefor the transport block through a rate matching algorithm based on thecoding rate of an MCS set reported from base station 100 and outputs thecoded bit sequence to modulation section 209-1.

Modulation section 209-1 for the transmission data modulates a certaintransport block at the same modulation level such as QPSK based on themodulation scheme of the MCS set reported from base station 100 andoutputs the transmission data symbol sequence obtained to DFT section210.

A symbol sequence having the same transmission format (MCS set) isgenerated in the transport block (codeword) of the transmissioninformation bit sequence through such channel coding and modulationprocessing. A multiplexing section may be provided between modulationsection 209-1 and DFT section 210 so that the multiplexing sectionmultiplexes a reference signal such as CAZAC (Constant Amplitude ZeroAuto Correlation) with the transmission data symbol sequence after thechannel coding and modulation processing.

DFT section 210 applies DFT to the transmission data symbol sequence,transforms the transmission data symbol sequence into subcarriercomponents (orthogonal frequency components) in the frequency domain andoutputs the subcarrier components to mapping section 212.

Channel coding section 208-2 for control data (resource allocationrequest information of PUSCH and PUCCH (scheduling request (SR) or thelike), ACK/NACK for DL transmission, CQI and CSI (Channel StateInformation) of the DL channel or the like) applies error correctingcoding such as convolutional coding to the control bit sequence of thecontrol data based on the coding rate of the MCS set reported from basestation 100 and then outputs the coded bit sequence to modulationsection 209-2.

Modulation section 209-2 for the control data performs modulation at amodulation level such as QPSK based on the modulation scheme of the MCSset reported from base station 100 and outputs the control data symbolsequence obtained to spreading section 211.

A control data symbol sequence having the same transmission format isalso generated in the transmission control bit sequence through thechannel coding and modulation processing. A multiplexing section may beprovided between modulation section 209-2 and spreading section 211 sothat the multiplexing section multiplexes a reference signal such asCAZAC with the control data symbol sequence after the channel coding andmodulation processing.

Spreading section 211 spreads symbols in a sequence having a constantamplitude characteristic in the time and frequency domains of the CAZACsequence or the like for the control data symbol sequence and outputsthe spread control data symbol sequence to mapping section 212.

Mapping section 212 maps the transmission data symbol sequence after DFTspreading (precoding) in the same transmission format inputted from DFTsection 210 and spreading section 211 and the spread control data symbolsequence in the CAZAC sequence to time and frequency resources of thePUSCH region or PUCCH region in one subframe (frequency divisionmultiplexing of the control signal and data signal) based on theresource mapping information inputted from control section 207 andoutputs the mapped control signal and data signal to IFFT section 213.The resource mapping information is information of the time andfrequency resources for mapping PUSCH and PUCCH allocated so as toperform frequency hopping between slots.

IFFT section 213 inserts 0's into subcarriers other than frequencyresources allocated to the terminal, then applies IFFT to therebygenerate a time domain SC-FDMA signal resulting from frequency divisionmultiplexing PUSCH and PUCCH and outputs the generated SC-FDMA signal toCP insertion section 214.

CP insertion section 214 adds a rear sample of 1 SC-FDMA block at thehead of the block as a cyclic prefix (CP) and outputs the SC-FDMA signalwith the CP added to radio transmission processing section 215.

Radio transmission processing section 215 converts the baseband signalof the SC-FDMA signal with the CP added to an RF signal and amplifiespower thereof by a power amplifier (PA) and transmits the RF signal fromtransmitting/receiving antenna port 201.

Next, a mapping pattern of inter-slot frequency hopping according to thepresent embodiment (hereinafter referred to as “inter-slot hoppingpattern”) will be described. Control section 207 stores the inter-slothopping pattern inside as a resource allocation rule and outputsresource mapping information based on the resource allocation rule tomapping section 212.

Mapping section 212 maps the PUSCH and PUCCH to time and frequencyresources based on the resource mapping information.

[Inter-Slot Hopping Oattern #1]

FIG. 5 is a diagram illustrating an example of inter-slot hoppingpattern #1 of PUSCH and PUCCH according to the present embodiment. Theexample shown in FIG. 5 shows a situation in which PUSCH to which a datasignal (control signal or control signal and data signal) is mapped andPUCCH to which a control signal is mapped are assumed to be one blockand this is cyclically frequency-shifted in the same direction (from thelow frequency to high frequency direction in FIG. 5) within an IFFT bandwhile maintaining frequency interval B and inter-slot frequency hoppingis thereby performed.

Both PUSCH and PUCCH shown in FIG. 5 span one subframe and aretransmitted in predetermined transmission formats respectively. That is,as shown in FIG. 5, in the first slot (first-half slot) and the secondslot (second-half slot) resulting from dividing one subframe into twoportions, signals of the same transmission format are allocated to thePUSCH and PUCCH respectively.

FIG. 5 shows an example where 12 data signals or control signals arespread by a DFT (3×3 DFT matrix) or CAZAC sequence having a sequencelength of 3 so that the spread data signal and control signal have asequence length of 12×3=36 (0 to 35) respectively. As shown in FIG. 5,the signal sequence is divided into two portions and the signalsequences are mapped to resources of the first slot (first-half slot)and second slot (second-half slot) in units of three continuous resourceelements in order from the frequency direction to the time direction.The values of resources where the signal sequence is not mapped are 0.Therefore, within the same SC-FDMA symbol, the data signal after DFTspreading and the control signal spread by a CAZAC sequence, which aremapped to the PUSCH and PUSCH regions, are frequency divisionmultiplexed.

As is clear from FIG. 5, the frequency difference between the PUCCH andPUSCH mapped to the PUCCH region located in a low frequency of the IFFTband in the first slot in one subframe is +B. In the second slot in onesubframe, the PUCCH which has inter-slot frequency hopped to the PUCCHregion located in a high frequency of the IFFT band cyclically maintainsfrequency interval +B from the PUSCH which has similarly inter-slotfrequency hopped in the IFFT band.

As shown in FIG. 5, by frequency division multiplexing the PUSCH andPUCCH and at the same time applying inter-slot frequency hopping theretowhile maintaining a frequency interval within the IDFT or IFFT band, itis possible to prevent the power distribution characteristic of the timewaveform of the frequency division multiplexed signal from changingbetween slots while obtaining frequency diversity effects throughfrequency hopping.

The reason will be described below. That is, a detailed description willbe given concerning the fact that inter-slot frequency hopping usinginter-slot hopping pattern #1 according to the present embodiment doesnot cause any change to the instantaneous power distributioncharacteristic of the time waveform of the frequency divisionmultiplexed signal, that is, the influence of the PUCCH and PUSCH on thechange in the time waveform of the frequency division multiplexed signalcan be limited to only the phase component.

N×1 time domain SC-FDMA signal vector d₀ in the first slot (slot #0)before inter-slot frequency hopping generated by applying IFFT afterfrequency division multiplexing the PUSCH and PUCCH can be expressed byequation 1. For simplicity, equation 1 shows d₀ in transmission signalexpression before CP insertion.

$\begin{matrix}\left( {{Equation}\mspace{14mu} 1} \right) & \; \\\begin{matrix}{d_{0} = {F^{- 1}\left( {D_{0,{PUSCH}} + D_{0,{PUCCH}}} \right)}} \\{= {d_{0,{PUSCH}} + d_{0,{PUCCH}}}}\end{matrix} & \lbrack 1\rbrack\end{matrix}$

In equation 1, F represents an N×N DFT matrix, N represents the numberof points of FFT (DFT). D_(0,PUSCH) (d_(0,PUSCH)) represents an N×1frequency domain (time domain) SC-FDMA signal vector before inter-slotfrequency hopping when a data signal is mapped to only the PUSCH regionand 0's are inserted in other resources, that is, when only PUSCH notsubjected to frequency division multiplexing is transmitted.

Similarly, D_(0,PUCCH) (d_(0,PUCCH)) represents an N×1 frequency domain(time domain) SC-FDMA signal vector before inter-slot frequency hoppingwhen a control signal is mapped to only the PUCCH region and 0's areinserted in other resources, that is, when only PUCCHs not subjected tofrequency division multiplexing are transmitted.

On the other hand, by cyclically frequency shifting the PUSCH and PUCCHas a block by S subcarriers in the same direction in the IFFT band, N×1time domain SC-FDMA signal vector d₁ can be expressed by equation 2 inthe second slot (slot #1) after performing inter-slot frequency hopping.

$\begin{matrix}\left( {{Equation}\mspace{14mu} 2} \right) & \; \\\begin{matrix}{d_{1} = {F^{- 1}{T^{(S)}\left( {D_{1,{PUSCH}} + D_{1,{PUCCH}}} \right)}}} \\{= {F^{- 1}T^{(S)}{F\left( {d_{1,{PUSCH}} + d_{1,{PUCCH}}} \right)}}} \\{= {{{diag}\left( {1,^{j\; 2\pi \; {S/N}},\ldots \mspace{14mu},^{j\; 2\pi \; {{S{({N - 1})}}/N}}} \right)}\left( {d_{1,{PUSCH}} + d_{1,{PUCCH}}} \right)}}\end{matrix} & \lbrack 2\rbrack\end{matrix}$

In equation 2, diag(a₀, a₁, . . . , a_(N−1)) represents a diagonalmatrix that has a₀, a₁, . . . , a_(N−1) as elements of the diagonalcomponent. Furthermore, T^((S)) is an N×N cyclic frequency shift matrixrepresenting a cyclic frequency shift of S subcarriers in the IFFT bandand is given by equation 3. When a cyclic frequency shift of S(>N)subcarriers (resource elements) greater than N is performed, a cyclicfrequency shift corresponding to T^((S mod N)) may be performed. Here,“mod” represents a modulo operation.

$\begin{matrix}\left( {{Equation}\mspace{14mu} 3} \right) & \; \\{T^{(S)} = \left( \begin{matrix}0 & \ldots & \ldots & 0 & 1 & 0 & \ldots & 0 \\\vdots & \; & \; & \; & \ddots & \ddots & \ddots & \vdots \\0 & \; & \; & \; & \; & \ddots & \ddots & 0 \\1 & \ddots & \; & \; & \; & \; & \ddots & 1 \\0 & \ddots & \ddots & \; & \; & \; & \; & 0 \\\vdots & \ddots & \ddots & \ddots & \; & \; & \; & \vdots \\0 & \ldots & 0 & 1 & 0 & \ldots & \ldots & 0\end{matrix} \right)} & \lbrack 3\rbrack\end{matrix}$

As shown in equation 3, a 0-th column vector of T^((S)) is comprised ofvectors in which elements of the 0-th row to (S−1)-th and elements of(S+1)-th to (N−1)-th rows are 0 and elements of only an S-th row are 1.Furthermore, other column vectors of T^((S)) are configured bycyclically shifting the 0-th column vector.

As is obvious from equation 1 and equation 2, the operation of providingthe PUCCH and PUSCH with the same cyclic frequency shift in the samedirection within the IFFT band, that is, applying inter-slot frequencyhopping to the PUCCH and PUSCH while maintaining the frequencydifference between them can limit the influence of the frequencydivision multiplexed signal on the change in the time waveform to onlythe phase components. That is, it is obvious that inter-slot frequencyhopping according to the present embodiment has no influence on theamplitude of the time domain SC-FDMA signal of the first slot and secondslot. Therefore, the distribution characteristic of the instantaneouspower of the time waveform of a transmission signal within one subframedoes not change between the first slot and second slot.

As shown in equation 4, inter-slot frequency hopping may also beperformed using T′^((S)) generated by multiplying cyclic frequency shiftmatrix T^((S)) in equation 3 by certain constant C whose absolute valueis 1. For example, C=exp(jD) (where D is a certain real number) or thelike is available as the constant. As is obvious by substituting T^((S))in equation 2 by T′^((S)), even in inter-slot frequency hopping usingT′^((S)), the distribution characteristic of instantaneous power of atime waveform of a transmission signal within one subframe does notchange between the first slot and the second slot.

$\begin{matrix}\left( {{Equation}\mspace{14mu} 4} \right) & \; \\{T^{\prime {(S)}} = {{CT}^{(S)} = {C\left( \begin{matrix}0 & \ldots & \ldots & 0 & 1 & 0 & \ldots & 0 \\\vdots & \; & \; & \; & \ddots & \ddots & \ddots & \vdots \\0 & \; & \; & \; & \; & \ddots & \ddots & 0 \\1 & \ddots & \; & \; & \; & \; & \ddots & 1 \\0 & \ddots & \ddots & \; & \; & \; & \; & 0 \\\vdots & \ddots & \ddots & \ddots & \; & \; & \; & \vdots \\0 & \ldots & 0 & 1 & 0 & \ldots & \ldots & 0\end{matrix} \right)}}} & \lbrack 4\rbrack\end{matrix}$

Therefore, when a transmission signal is transmitted over the first slotand second slot in the same transmission format, distortion of thetransmission signal caused by non-linearity of the PA can be equalizedfor the first slot and the second slot and it is possible to avoiddeterioration of receiving quality caused when the non-linear distortioncharacteristic received by a transmission signal transmitted over thefirst slot and second slot in the same transmission format changesbetween slots. Furthermore, since the non-linear distortioncharacteristic received by a transmission signal transmitted in the sametransmission format is uniform between the first slot and the secondslot, it is possible to steadily perform optimum control ofpre-distortion from the first slot to the second slot.

As described above, according to the present embodiment, mapping section212 arranges PUCCH in a frequency resource of the first slot, arrangesPUSCH in a frequency resource located predetermined frequency interval Bapart from the frequency resource out of the frequency resources of thefirst slot in which PUCCH is arranged and cyclically frequency shiftsand arranges PUCCH and PUSCH within the IDFT or IFFT bandwidth whilemaintaining predetermined frequency interval B in the frequencyresources of the second slot, and can thereby cause the PUCCH and PUSCHto frequency hop between the first slot and the second slot.

This makes it possible to prevent changes in the instantaneous powerdistribution characteristic of the time waveform of the frequencydivision multiplexed signal between slots while obtaining a frequencydiversity effect through inter-slot frequency hopping. Therefore, it ispossible to equalize distortion of the transmission signal caused by thenon-linear distortion characteristic of the PA between the first slotand the second slot and prevent deterioration of receiving qualitycaused by a change of the non-linearity characteristic received by thetransmission signal transmitted in the same transmission format over thefirst slot and the second slot. Furthermore, it is possible to steadilyperform optimum control of pre-distortion over the first and the secondslots.

Frequency interval B between the first channel and the second channelallocated to the first slot may be one of B₀ and B₁ as shown in FIG. 6as long as it is a cyclically continuous frequency interval within theIFFT band.

Furthermore, the number of channels transmitted through frequencydivision multiplexing may be three or more. As shown in FIG. 7, whenthree channels are allocated, if the frequency interval between thefirst channel and the second channel in the first slot is +B₀ and thefrequency interval between the second channel and the third channel is+B₁, the second channel may be cyclically allocated to a frequencyresource located +B₀ apart from the first channel and the third channelmay be cyclically allocated to a frequency resource located +B₁ apartfrom the second channel within the IDFT or IFFT bandwidth in the secondslot. When three or more channels are subjected to frequency divisionmultiplexing and inter-slot frequency hopping, this makes it possible toobtain effects similar to those with two channels.

A case has been described above where the PUSCH and PUCCH are cyclicallyfrequency shifted by S subcarriers in the same direction within the IFFTband, but the amount of cyclic frequency shift may be one of +S and −Ssubcarriers. Since −S mod N=(N−S) mod N, that is, the cyclic frequencyshift of −S (<0) subcarriers is equivalent to the cyclic frequency shiftof (N−S) (>0). Therefore, as is clear from equation 2, whether theamount of cyclic frequency shift is +S or −S, the influence on the timedomain SC-FDMA signal in the second slot is limited to only the phasecomponent (in the case of the cyclic frequency shift of −S subcarriers,S in equation 2 is simply substituted by (N−S)) and there is noinfluence on the magnitude of the amplitude. This gives effects similarto those described above.

In the inter-slot hopping pattern shown in FIG. 5, when the frequencydifference from the frequency resource to which PUSCH is allocated inthe first slot to the frequency resource to which PUCCH is allocated is+B (−B), it is possible to say that the PUCCH is cyclically allocated tothe frequency resource located +B (−B) apart from the PUSCH in thesecond slot within the IDFT or IFFT bandwidth.

When a plurality of signals mapped to the PUSCH and PUCCH in the slotinclude a specific signal sequence (=deterministic signal) such as areference signal using a CAZAC sequence and stochastically changingsignal sequence (stochastic signal) such as data signal and controlsignal (CQI, CSI, ACK/NACK or the like), and when deterministic signals(e.g. reference signals), stochastic signals and deterministic signaland stochastic signal are frequency division multiplexed within the sameSC-FDMA signal, the above-described effect is obtained by applying aninter-slot hopping pattern as shown in FIG. 5. FIG. 8 shows an exampleof frequency division multiplexing in this case. FIG. 8 is an examplewhere signals having different statistic properties are frequencydivision multiplexed.

FIG. 8 shows a case where reference signals (deterministic signals) ofCAZAC sequence or the like are mapped to second and third SC-FDMAsymbols of the PUCCH in the first slot, eighth and ninth SC-FDMA symbolsof the PUCCH in the second slot, third SC-FDMA symbol of the PUSCH inthe first slot and ninth SC-FDMA symbol of the PUSCH in the second slotand stochastic signals such as different data signals (control signals)are mapped to other resources of the PUSCH and PUCCH. Therefore, FIG. 8shows a case where data signals or the like (stochastic signals) arefrequency division multiplexed in the 0-th, first, fourth, fifth, sixth,seventh, tenth and eleventh SC-FDMA symbols, data signals (stochasticsignals) and reference signals (deterministic signals) are frequencydivision multiplexed in the second and eighth SC-FDMA symbols andreference signals (deterministic signals) are frequency divisionmultiplexed in the third and ninth SC-FDMA symbols, and transmitted.

Next, a control procedure when performing inter-slot frequency hoppingaccording to the present embodiment will be described.

FIG. 9 is a sequence diagram showing an example of control procedure.

<1> Terminal 200 transmits allocation requests for both (a plurality of)PUCCHs and (a plurality of) PUSCH resources.

<2> Base station 100 determines, based on these allocation requests, (1)the presence or absence of indication of frequency hopping of PUSCH andPUCCH, (2) amount of cyclic frequency shift of inter-slot frequencyhopping of PUSCH and PUCCH when performing frequency hopping and (3) ULPUSCH and PUCCH allocation resources.

<3> Base station 100 reports the information (inter-slot frequencyhopping information) to terminal 200 through a DL control channel (PDCCHor the like).

<4> Terminal 200 frequency-division-multiplexes and transmits UL PUCCHand PUSCH based on the reported resource allocation information of PUCCHand PUSCH and the amount of cyclic frequency shift of inter-slotfrequency hopping or the like.

The control procedure when performing inter-slot frequency hopping isnot limited to the above-described one, but the following procedures mayalso be adopted.

[When Index Number of (Logical) Control Channel Used for PDCCH isAssociated with Resource Number of PUCCH]

For example, UL ACK/NACK transmission of LTE corresponds to this. Thecontrol procedure in this case will be described using FIG. 10 and FIG.11.

<1> Terminal 200 transmits an allocation request for (a plurality of)PUSCH resources.

<2> Base station 100 determines, based on the allocation request, (1)the presence or absence of indication of frequency hopping of PUSCH andPUCCH, (2) when frequency hopping is performed, the amount of cyclicfrequency shift of inter-slot frequency hopping of PUSCH and PUCCH and(3) UL PUSCH and PUCCH resource allocation.

The following two methods are available as the method of determining (3)UL PUSCH and PUCCH resource allocation.

Base station 100 determines resources in order of PUCCH resources andPUSCH resources (see FIG. 10). To be more specific, PUSCH whichsatisfies the resource allocation rule according to the presentembodiment is selected from the resource number of the PUCCH used forfrequency division multiplexing transmission associated with the indexnumber of a DL (logic) control channel used in the PDCCH.

Base station 100 determines resources in order of PUSCH resources andPUCCH resources (see FIG. 11). To be more specific, resource allocationis determined for the PUSCH to be subjected to frequency hopping, PUCCHresources that satisfy the resource allocation rule according to thepresent embodiment are selected based on the resources to which thePUSCH is allocated and the index number of the DL (logic) controlchannel associated with the resource number is calculated.

<3> Base station 100 transmits control information of DL/UL transmissionthrough a control channel (PDCCH) corresponding to a certain indexnumber of the DL (logic) control channel through which controlinformation for DL transmission and (or) control information for ULtransmission is transmitted.

<4> Terminal 200 blind-decodes a plurality of DL (logic) control channelcandidates and thereby detects a DL/UL control signal directed to theterminal. To decide the presence or absence of a DL/UL control signaldirected to the terminal, an identification number specific to theterminal or CRC (Cyclic Redundancy Check) or the like masked with anidentification number is used.

Terminal 200 then detects PUCCH resource number allocated from the indexnumber of the DL (logic) control channel detected through blinddecoding. Furthermore, terminal 200 extracts information of PUSCHresources reported through the DL control channel.

Upon detecting a control signal directed to the terminal, terminal 200transmits control information (ACK/NACK or the like for DL datatransmission) through the UL control channel using resources of the UL(logic) control channel (or UL physical control channel (PUCCH)) after aplurality of subframes associated with an index number of the DL (logic)control channel.

<5> Terminal 200 frequency-division-multiplexes and transmits UL PUCCHand PUSCH.

[When UL PUCCH Resources are Reserved]

When UL PUCCH resources are reserved and allocated beforehand forcertain terminal 200, a control procedure shown below may also be used.The control procedure in this case will be described using FIG. 12.

<1> Terminal 200 transmits allocation requests for (a plurality of)PUSCH resources.

<2> Base station 100 determines (1) the presence or absence ofindication of frequency hopping of PUSCH and PUCCH based on theallocation request.

Furthermore, base station 100 calculates PUSCH resources that satisfy aresource allocation rule based on the reserved PUCCH resources (andhopping pattern information of the resources) and allocates a PUSCHhopping pattern (amount of cyclic frequency shift, resources of PUSCH)((2), (3)).

<3> Base station 100 reports resource allocation of UL PUSCH, presenceor absence of indication of frequency hopping of PUSCH and PUCCH andinformation (inter-slot frequency hopping information) of an amount ofcyclic frequency shift of inter-slot frequency hopping of PUSCH andPUCCH to terminal 200 using a DL (logic) control channel.

<4> Terminal 200 calculates allocated PUSCH resources and reserved PUCCHresources.

<5> Terminal 200 frequency-division-multiplexes and transmits UL PUCCHand PUSCH using the calculated PUSCH resources and reserved PUCCHresources.

Next, information included in the inter-slot frequency hoppinginformation reported through a control procedure will be described.

A case has been described in the above-described example of the controlprocedure where base station 100 reports the following inter-slotfrequency hopping information to terminal 200 explicitly or implicitlyto thereby perform frequency division multiplexing transmission applyingUL inter-slot frequency hopping.

[1] PUCCH and PUSCH resource allocation information (see FIG. 9), PUSCHresource allocation information and PUCCH resource allocationinformation associated with DL (logic) control channel (see FIG. 10 andFIG. 11) or PUSCH resource allocation information and reserved PUCCHresource allocation information (see FIG. 12).

[2] Amount of cyclic frequency shift used for inter-slot frequencyhopping of PUSCH and PUCCH

[3] Presence or absence of indication of frequency hopping of PUSCH andPUCCH

Hereinafter, such report information will be described.

[1] Regarding Reporting of Resource Allocation Information

In the control procedure in FIG. 9, for example, frequency resources towhich PUSCH and PUCCH are mapped in the first slot may be reported asPUSCH and PUCCH resource allocation information. The PUSCH and PUCCHfrequency resource allocation information in the second slot can becalculated by giving an amount of cyclic frequency shift which will bedescribed later to frequency resources in the first slot. For example,in the case where the amount of cyclic frequency shift is S, thefrequency resource allocation information can be expressed by secondslot frequency resource number [a1, b1, c1] =first slot allocationfrequency resource number [a0, b0, c0]+amount of cyclic frequency shift[S, S, S]=[a0+S, b0+S, c0+S].

Furthermore, as shown in FIG. 10 and FIG. 11, when an index number ofthe DL (logic) control channel is associated with a resource number (andinter-slot frequency hopping pattern) of the PUCCH or, as shown in FIG.12, when resources (and inter-slot frequency hopping pattern) of PUCCHare reserved beforehand, only resource allocation information of thePUSCH in the first slot may be directly (explicitly) reported andresource allocation information of the PUCCH may be indirectly(implicitly) reported via a DL (logic) control channel. Frequencyresources in the second slot can be calculated by giving an amount ofcyclic frequency shift, which will be described later, to the frequencyresources in the first slot as in the case of FIG. 9.

[2] Regarding Reporting of Amount of Cyclic Frequency Shift

In the case of FIG. 9, as information for reporting the amount of cyclicfrequency shift used for inter-slot frequency hopping of PUSCH andPUSCH, respective frequency resources of the PUCCH and PUSCH allocatedto the first slot and frequency difference (amount of cyclic frequencyshift) between the respective frequency resources of the PUCCH and PUSCHallocated to the second slot after frequency hopping may be reported.Since the present invention features frequency hopping by making thesame frequency shift between slots while maintaining a frequencyinterval between the PUCCH and PUCCH, the same values may be transmittedas the respective amounts of cyclic frequency shift of the PUCCH andPUSCH. The terminal may perform slot frequency hopping of the PUSCH andPUCCH based on the two (PUCCH and PUSCH) same reported amounts of cyclicfrequency shift. This makes it possible to secure backward compatibilitywith LTE which adopts a configuration of independently controllingfrequency hopping of the PUCCH and PUSCH. Furthermore, the terminal canreceive control a signal with higher reliability by combining signalsindicating the two received amounts of cyclic frequency shift. FIG. 13shows a sequence diagram of control information in this case.

Furthermore, taking advantage of the feature of the present invention,that is, the fact that the amount of cyclic frequency shift of the PUCCHbetween slots is the same as the amount of cyclic frequency shift of thePUSCH between slots, a configuration of reporting only the amount ofcyclic frequency shift common to the PUSCH and PUCCH (that is, one ofthe amounts of cyclic frequency shift) may be adopted. This makes itpossible to reduce the amount of control information related to theamounts of cyclic frequency shift of PUSCH and PUSCH.

FIG. 14 shows a sequence diagram of the control signal in this case.

As shown in FIG. 10 or FIG. 11, when the index number of the DL (logic)control channel is associated with the resource number (and inter-slotfrequency hopping pattern) of the PUCCH or, as shown in FIG. 12, alsowhen PUCCH resources (and inter-slot frequency hopping pattern) arereserved and allocated beforehand, the same values may be reported asthe amounts of cyclic frequency shift of the PUCCH and PUSCH.Furthermore, taking advantage of the fact that the amount of cyclicfrequency shift of the PUCCH is the same as the amount of cyclicfrequency shift of the PUSCH; only the amount of cyclic frequency shiftcommon to the PUSCH and PUCCH (that is, one of the amounts of frequencyshift) may be reported.

Moreover, in addition to the resource number of the PUCCH, when theindex number of the DL (logic) control channel is associated with theinter-slot frequency hopping pattern of the PUCCH (amount of cyclicfrequency shift) or when the inter-slot frequency hopping pattern of thePUCCH (amount of cyclic frequency shift) is reserved beforehand, theamount of cyclic frequency shift between slots of the PUCCH may be setas the amount of cyclic frequency shift of the PUSCH, and therefore theamount of cyclic frequency shift of the PUSCH need not be reported inaddition to the resource number and amount of cyclic frequency shift ofthe PUCCH. This makes it possible to further reduce the amount ofcontrol information.

By setting the amount of cyclic frequency shift common to the PUCCH andPUSCH as a value common to a plurality of cell-specific users, setting,for example, the amount of cyclic frequency shift in association withthe identification number of the cell, it is possible to further reducethe amount of control information related to the amount of cyclicfrequency shift while simultaneously and easily obtaining the effects ofthe present invention for a plurality of usersfrequency-division-multiplexed and transmitted.

[3] Regarding Reporting of Presence or Absence of Indication ofInter-Slot Frequency Hopping

As in the above-described case of reporting the amount of cyclicfrequency shift, the present invention causes the PUSCH and PUCCH tosimultaneously perform frequency hopping while maintaining a frequencyinterval between the PUSCH and PUCCH, and can thereby also reducecontrol information by sharing identification numbers of the presence orabsence of indication of inter-slot frequency hopping of the PUSCH andPUSCH.

(Other Variations)

Hereinafter, other variations of inter-slot hopping pattern will bedescribed.

[Inter-Slot Hopping Pattern #2]

FIG. 15 to FIG. 17 show an example of [inter-slot hopping pattern #2].

FIG. 7 described above shows an example where one channel is mapped toPUCCH and two channels are mapped to PUSCH (that is, a case of frequencydivision multiplexing transmission of PUSCH

PUCCH). In addition to such mapping, the present invention is alsoapplicable to a case where a carrier aggregation technique as shown inFIG. 15 to FIG. 17 is used for the purpose of improving the transmissionrate by transmitting a plurality of component bands bundled together andeffects similar to those described in [inter-slot hopping pattern #1]can be obtained.

Frequency Division Multiplexing Transmission of a Plurality of PUCCHs(See FIG. 15)

Two PUCCH regions defined per component band are subjected to inter-slotfrequency hopping while maintaining frequency difference +B₀. However,for PUCCH per component band, the PUCCH region defined within thecomponent band is subjected to inter-slot frequency hopping. FIG. 15shows an example where PUCCH regions are defined at both edges ofcomponent bands #0 and #1 respectively.

Frequency Division Multiplexing Transmission of a Plurality of PUSCHs(See FIG. 16)

One PUSCH region defined per component band is subjected to inter-slotfrequency hopping while maintaining the frequency difference. However,for PUSCH per component band, a PUSCH region defined per component bandis subjected to inter-slot frequency hopping. FIG. 16 is an examplewhere a PUSCH region is defined in the middle of component bands #0 and#1 respectively.

Frequency Division Multiplexing Transmission of a Olurality of PUCCHsand a Plurality of PUSCHs (Combination of FIG. 15 and FIG. 16)

By combining the examples shown in FIG. 15 and FIG. 16, it is possibleto realize a plurality of PUCCHs and a plurality of PUSCHs to besubjected to inter-slot frequency hopping within a component band over aplurality of component bands.

A case is described in the examples shown in FIG. 15 and FIG. 16 whereeach PUCCH and each PUSCH are subjected to inter-slot frequency hoppingwithin a component band, but as shown in FIG. 17, a configuration mayalso be adopted in which PUCCH and PUSCH are subjected to inter-slotfrequency hopping between a plurality of component bands. FIG. 17 showsa case where PUCCH is subjected to inter-slot frequency hopping betweencomponent band #0 and component band #1 and PUSCH is subjected tointer-slot frequency hopping within component band #0. This makes itpossible to accommodate a terminal (LTE-Advanced terminal) thattransmits a plurality of component bands bundled together and a terminal(e.g. LTE terminal) that performs transmission using only one componentband in the same PUCCH region while obtaining effects similar to thoseof the inter-slot hopping patterns shown in FIG. 15 and FIG. 16. Thatis, backward compatibility with LTE can further be secured. Furthermore,since a plurality of PUCCH regions (PUSCH regions) present in differentcomponent bands can be flexibly allocated, it is possible to avoidtraffic from being concentrated on a PUCCH region (PUSCH region) in acertain specific component band.

The control procedure and report information in the above-describedcarrier aggregation may be controlled per component band of UL using aDL control channel (PDCCH) in the same way as for the control procedureshown in FIG. 9, FIG. 10, FIG. 11 and FIG. 12.

Furthermore, since FIG. 15 to FIG. 17 correspond to a case where thepresent invention is applied over a plurality of component bands, theamount of inter-slot cyclic frequency shift is the same for PUCCH andPUSCH per component band. Therefore, when the presence or absence ofindication of inter-slot frequency hopping and the amount of cyclicfrequency shift are set to be the same for each of a plurality ofcomponent bands, it is possible to further secure backward compatibilitywith the control method of LTE that controls inter-slot frequencyhopping per component band.

Furthermore, it may also be possible to bundle a plurality of componentbands, make the same setting about the presence or absence of indicationof inter-slot frequency hopping and the amount of cyclic frequencyshift, report and control the report information collectively asindication information of inter-slot frequency hopping and a commonamount of cyclic frequency shift. For example, when a plurality ofcomponent bands are bundled and subjected to carrier aggregation, theamount of cyclic frequency shift of each PUCCH or each PUSCH present ina plurality of component bands may be reported as an amount of cyclicfrequency shift (one amount of cyclic frequency shift is defined/set ina plurality of component bands) common to all bands. Thus, when carrieraggregation is performed, it is possible to reduce the amount of controlinformation related to UL frequency hopping of PUSCH or PUCCH reportedthrough the DL control channel.

Furthermore, as described above, by setting the same amount of cyclicfrequency shift for PUCCH and PUSCH common to a plurality ofcell-specific users, for example, setting an amount of cyclic frequencyshift in association with an identification number of the cell, it ispossible to further reduce the amount of control information related tothe amount of cyclic frequency shift while simultaneously and easilyobtaining the effects of the present invention for a plurality of userssubjected to carrier aggregation and frequency division multiplexingtransmission.

[Inter-Slot Hopping Pattern #3]

FIG. 18 shows an example of [inter-slot hopping pattern #3].

As shown in FIG. 18, when the frequency difference between a frequencyresource to which a first channel is allocated in the first slot and afrequency resource to which a second channel is allocated is +B, thesecond channel is cyclically allocated to a frequency resource located−B apart from the first channel in the second slot within the IDFT orIFFT bandwidth.

Thus, when frequency interval B between the PUCCH and PUSCH in the firstslot is equal to or below the total bandwidth (=X₀+X₁) of the PUCCHdefined at both edges of the IFFT band, it is possible to avoid a casewhere the PUSCH is mapped to the PUCCH region in the second slotdepending on the inter-slot frequency hopping pattern (amount of cyclicfrequency shift) of the PUCCH and obtain effects similar to the effectsdescribed in [inter-slot hopping pattern #1] when the signal mapped tothe PUCCH and PUSCH is a signal that stochastically changes.

Furthermore, it is also possible to adaptively switch between theinter-slot frequency hopping method having frequency difference +B inthe first slot and frequency difference +B in the second slot as shownin [inter-slot hopping pattern #1] and the inter-slot frequency hoppingmethod having frequency difference +B in the first slot and frequencydifference −B in the second slot as shown in [inter-slot hopping pattern#3]. Thus, even when mapping a signal sequence in which signals of aplurality of different characteristics (stochastic signal, deterministicsignal or the like) coexist to PUCCH and PUSCH, it is possible to selectinter-slot frequency hopping that minimizes a change in theinstantaneous power of the transmission signal waveform between slots.

[Inter-Slot Hopping Pattern #4]

FIG. 19 shows an example of [inter-slot hopping pattern #4].

Frequency interval B between the first channel and second channel is setto no less than a maximum value of the total bandwidth of the PUCCHregion cyclically and continuously present in the IFFT (IDFT) bandwidth.

FIG. 19 shows a case where the bandwidth of PUCCH region #0 present in alow frequency of the IFFT band is X₀ and the bandwidth of PUCCH region#1 present in a high frequency of the IFFT band is X₁. As shown in FIG.19, frequency interval B between PUCCH and PUSCH in the first slot isset to no less than total bandwidth (X₀+X₁) of the PUCCH regioncyclically and continuously present in the IFFT (IDFT) bandwidth. Thismakes it possible to avoid the inter-slot frequency hopped PUSCH frombeing mapped to PUCCH region #0 and PUCCH region #1 specially providedfor mapping a control signal to PUCCH region #1 while causing the PUCCHto perform inter-slot hopping in the second slot.

Furthermore, frequency interval B between the first channel and secondchannel may also be set to no less than a value (X₀+X₁−Y in FIG. 19)resulting from subtracting PUCCH bandwidth Y from a maximum value of thetotal bandwidth of the PUCCH region cyclically and continuously presentin the IFFT (IDFT) bandwidth. This widens the degree of freedom in thesetting of frequency interval B between the first channel and secondchannel, and can thereby reduce constraints in frequency resourceallocation in the first channel and second channel in the first slot.

[Inter-Slot Hopping Pattern #5]

FIG. 20 shows an example of [inter-slot hopping pattern #5].

Frequency interval B between the first channel and second channel is setto no less than the total bandwidth of the PUCCH region and/or guardband (zero padding) cyclically and continuously present in the IFFT(IDFT) bandwidth.

FIG. 20 shows a case where the bandwidth of guard band (zero padding)region 0 present in a low frequency of the IFFT band is Y₀, thebandwidth of PUCCH region #0 is X₀, the bandwidth of guard band (zeropadding) region #1 present in a high frequency of the IFFT band is Y₁and the bandwidth of PUCCH region #1 is X₁. As shown in FIG. 20,frequency interval B between PUCCH and PUSCH in the first slot is set tono less than the total bandwidth (X₀+X₁+Y₀+Y₁) of guard band (zeropadding) region #0, guard band (zero padding) region #1, PUCCH region #0and PUCCH region #1 cyclically and continuously present in the IFFT(IDFT) bandwidth. This makes it possible to avoid the inter-slotfrequency hopped PUSCH from being mapped to PUCCH region #0, PUCCHregion #1, guard band (zero padding) region #0 and guard band (zeropadding) region #1 specially provided for mapping a control signal whilecausing PUCCH to perform inter-slot hopping to PUCCH region #1 in thesecond slot.

FIG. 20 shows a case where the PUCCH region is located adjacent to theguard band region, but when these regions are not located adjacent toeach other and PUCCH regions and guard band regions are present in aplurality of bands (when these regions are continuous to a discontinuousfrequency band), frequency interval B may be set to no less than amaximum total bandwidth of the continuous PUCCH region and/or guard bandregion, and it is thereby possible to obtain effects similar to thosewhen the PUCCH region and the guard band region are located adjacent toeach other.

For example, when a carrier aggregation technique for realizing highspeed transmission is used by bundling the plurality of component bandsshown in, for example, FIG. 15 and FIG. 16, if leakage interference froman LTE system comprised of only one component band to an LTE-advancedsystem or conversely leakage interference from an LTE-advanced system toan LTE system is taken into account, a case is assumed where a guardband is provided between component bands. That is, in FIG. 15 and FIG.16, a case is assumed where a guard band (zero padding that makes thesubcarrier component 0) region is provided between PUCCH region #0 ofneighboring component band #0 and PUCCH region #1 of component band #1.In such a case, the total bandwidth of PUCCH region #0 of component band#0 and PUCCH region #1 of the guard band region and component band #1cyclically and continuously present in the center of the IFFT band iswider than the total bandwidth of PUCCH region #0 of component band #0and PUCCH region #1 of component band #1 cyclically and continuouslypresent at both edges of the IFFT band. Therefore, in theabove-described case, frequency interval B may be set to no less than amaximum total bandwidth of the continuous PUCCH region and/or guard bandregion, that is, the total bandwidth of PUCCH region #0 of componentband #0, guard band region and PUCCH region #1 of component band #1cyclically and continuously present in the center of the IFFT band.

Furthermore, frequency interval B between the first channel and secondchannel may be set to no less than a value resulting from subtractingPUCCH bandwidth Z from a maximum value of the maximum total bandwidth ofthe PUCCH region and/or guard band region cyclically and continuouslypresent in the IFFT (IDFT) bandwidth (X₀+X₁+Y₀+Y₁−Z in the case of FIG.20). This widens the degree of freedom in the setting of frequencyinterval B between the first channel and second channel, and can therebyreduce constraints of frequency resource allocation of the first channeland second channel in the first slot.

[Inter-Slot Hopping Pattern #6]

FIG. 21 shows an example of [inter-slot hopping pattern #6].

Suppose the signal mapped in the first channel in the second slot afterinter-slot frequency hopping (or second channel in the second slot) is asignal that repeats a signal mapped in the first channel in the firstslot (or second channel in the first slot).

FIG. 21 shows a situation in which inter-slot frequency hopping isapplied to signals of #0 to 2, #6 to 11 and #15 to 17 out of signalsmapped to each allocation unit of the PUCCH region in the first slotwhile maintaining a frequency interval between PUCCH and PUSCH and thenthe same signal is repeatedly mapped also in the PUCCH region of thesecond slot. Thus, by combining repetition signals in the first slot andthe second slot while maintaining a distribution of instantaneous powervariation of the inter-slot frequency multiplexing division multiplexedsignal, it is possible to obtain frequency and time diversity effects.

An example of the method of generating a repetition signal to be mappedto the first slot and the second slot is shown below.

[1] A modulated symbol is replicated without being spread and thereplicated modulated symbol is mapped to the first slot and second slotas is.

[2] By spreading the modulated symbol with one certain spreadingsequence such as a DFT or CAZAC sequence and duplicating the spreadsignal, a plurality of repetition signals are generated and mapped tothe first slot and second slots respectively. A configuration may alsobe adopted in which a bit sequence before channel coding or a bitsequence after channel coding and before modulation is replicated, thereplicated bit sequences are modulated, the modulated symbols are spreadby one certain spreading sequence such as DFT or CAZAC sequence, aplurality of repetition signals are generated and mapped to the firstslot and second slot respectively.

By generating a repetition signal using the above-described methods in[1] and [2], the instantaneous power distribution characteristic (e.g.CCDF characteristic of PAPR) of the SC-FDMA time waveform is acorrelated (similar) characteristic between the first slot and secondslot, and can thereby prevent a drastic change of an inter-slotinstantaneous power distribution characteristic.

[3] A modulated symbol is replicated, the replicated modulated symbolsare spread by a spreading sequence which differs from one slot toanother, and the spread signals are mapped to the first slot and secondslot. A configuration may also be adopted in which a bit sequence beforechannel coding or a bit sequence after channel coding and beforemodulation is replicated, the replicated bit sequences are modulated andthen the modulated symbols are spread by a spreading sequence whichdiffers from one slot to another, a plurality of repetition signals aregenerated and mapped to the first slot and second slot.

By generating a repetition signal using the above-described method in[3], it is possible to obtain effects similar to the effects describedin [inter-slot hopping pattern #1] when signals mapped to PUCCH andPUSCH are signals that change stochastically while randomizinginterfered (e.g. other cell interference) components between the firstslot and second slot.

[Inter-Slot Hopping Pattern #7]

A signal mapped to at least one channel of the first channel and secondchannel is a signal spread by one certain code sequence such as DFT orCAZAC sequence.

Explaining this using, for example, above-described FIG. 5, onemodulated data symbol is spread (N=3) with a 3×3 DFT matrix and a signalsequence having a length of 3 is mapped to frequency resources of PUSCH(e.g. resource elements 0 to 2 of the 0-th SC-FDMA symbol). Similarly,one modulated control symbol is spread by a CAZAC sequence having asequence length of 3 and the spread signal sequence having a length of 3is mapped to PUCCH frequency resources (e.g. resource elements 0 to 2 ofthe 0-th SC-FDMA symbol).

Thus, by mapping each spread signal sequence to frequency resources(continuous), each signal sequence can generate a signal sequence havinga high correlation among neighboring frequency resources, and thereforean amplitude variation width of a time domain signal of each spreadsignal sequence is reduced. Therefore, the amplitude variation width ofthe frequency-division-multiplexed signal corresponding to a signalgenerated by combining a plurality of those signals is smaller than anunspread signal. That is, it is possible to obtain a frequency diversityeffect by inter-slot frequency hopping while reducing the instantaneouspower variation width of the transmission signal waveform per slot andfurther obtain an effect of being able to reduce changes in aninstantaneous power variation distribution of the transmission timewaveform of an inter-slot frequency-division-multiplexed signal.

[Inter-Slot Hopping Oattern #8]

Of the plurality of inter-slot frequency hopped channels, suppose asignal mapped to two or more discontinuous channels is a signalresulting from dividing a signal (spectrum) spread by a code sequence ofa DFT or CAZAC sequence or the like.

A case has been described in above-described FIG. 5 where a DFT-spreadinformation signal sequence is mapped to PUSCH and a control signalsequence is mapped to PUCCH through a CAZAC sequence, but signals mappedto a plurality of PUSCHs present in the PUSCH region in the first slotmay be one of the following signals.

[1] Suppose signals to be mapped to two or more discontinuous channelsare signals resulting from spectrum dividing the DFT-spread signal intoa plurality of clusters in the frequency domain (Cluster-SC-FDMA signal,cluster SC-FDMA signal).

FIG. 22 is an example where one modulated symbol is spread (N=5) by a5×5 DFT matrix, the spread signal sequence having a length of 5 isdivided into 3:2 (e.g. 0 to 2 and 3 to 4) and are mapped to allocationunits of the SC-FDMA symbol at the heads of the second channel and thirdchannel of PUSCH.

FIG. 22 is an example where similar processing is performed onsubsequent SC-FDMA symbols and then inter-slot frequency hopping similarto the case with three channels described in [inter-slot hopping pattern#1] is applied.

FIG. 23 shows a configuration example of the terminal in this case. InFIG. 23, components common to those in FIG. 4 will be assigned the samereference numerals as those in FIG. 4 and descriptions thereof will beomitted. Terminal 200A in FIG. 23 adopts a configuration in whichspectrum division section 216 that divides a signal sequence after DFTis added to terminal 200 in FIG. 4 between DFT section 210 and mappingsection 212.

[2] Suppose signals to be mapped to two or more discontinuous channelsare signals (N×SC-FDMA signals) resulting from individually DFTspreading a signal sequence generated independently by channel coding ormodulating two or more different transport blocks (codewords) in adifferent or the same transmission format (MCS set or transmission powercontrol value).

In this case, in FIG. 16 shown above, respective DFT-spread signalsequences corresponding to two or more different transport blocks(codewords) may be mapped to two or more PUSCHs (first channel, secondchannel, . . . ).

By mapping the above-described signals as shown in [1] or [2] andcausing the signals to frequency hop between slots, even when thesignals are mapped to two or more discontinuous channels, it is possibleto suppress changes in the distribution characteristic of instantaneouspower between slots while maintaining resource allocation flexibility inthe frequency domain without leading to a drastic increase of PAPRcompared to OFDM transmission.

By arranging two or more discontinuous channels to which a DFT-spreadsequence is mapped at equal intervals in the frequency domain, it ispossible to further avoid changes in the distribution characteristic ofinstantaneous power between slots while maintaining the distributioncharacteristic of instantaneous power of lower PAPR.

A method of reporting an amount of cyclic frequency shift using thefeature of the present invention, that is, that the amount of cyclicfrequency shift of PUCCH between slots is the same as the amount ofcyclic frequency shift of PUSCH between slots has been described above.To be more specific, descriptions have been given about a method ofsetting the amount of cyclic frequency shift of PUSCH and the amount ofcyclic frequency shift of PUCCH to the same value and reporting theamounts and a method of reporting only the amount of cyclic frequencyshift common to PUSCH and PUCCH (that is, one of the amounts of cyclicfrequency shift). In the case of setting the amount of cyclic frequencyshift of PUSCH and the amount of cyclic frequency shift of PUCCH to thesame value and reporting both, the terminal combines the same tworeceived amounts of cyclic frequency shift, and can thereby improvereceiving quality of the information. However, a case may also beassumed where inter-slot frequency hopping patterns (cyclic frequencyshifts) of a plurality of PUSCHs and a plurality of PUCCHs aretransmitted through the same component carrier (component band) ordifferent component carriers (component bands) on a DL and reported atdifferent times and the inter-slot frequency hopping patterns of theplurality of channels are not the same at a certain point in time offrequency division multiplexing transmission on an UL. In such a case,inter-slot frequency hopping may be performed on a plurality of channelsaccording to the following method.

(1) When a plurality of PUSCHs are simultaneously transmitted throughthe same component carrier or different component carriers, all of theplurality of PUSCHs are inter-slot frequency hopped preferentiallyfollowing an inter-slot frequency hopping pattern (cyclic frequencyshift) of PUSCH reported by the primary component carrier (PCC) of a DLpreferentially received and monitored by the terminal with. This makesit possible to obtain effects similar to those described above.

(2) When PUSCH and PUCCH (PUCCH and PUCCH) are simultaneouslytransmitted through the same component carrier, PUSCH and PUCCH (PUCCHand PUCCH) are inter-slot frequency hopped preferentially following aninter-slot frequency hopping pattern of (one certain) PUCCH reported.This makes it possible to obtain effects similar to those describedabove.

(3) When a plurality of PUSCHs and a plurality of PUCCHs aresimultaneously transmitted through the same component carrier ordifferent component carriers, all the channels are inter-slot frequencyhopped following an inter-slot frequency hopping pattern (cyclicfrequency shift) of PUCCH reported by the primary component carrier of aDL preferentially received and monitored by the terminal. This makes itpossible to obtain effects similar to those described above.

FIG. 18 has described the method of cyclically allocating the secondchannel to a frequency resource located frequency difference −B apartfrom the first channel in the second slot within the IDFT or IFFTbandwidth when the frequency difference between the frequency resourceto which the first channel is allocated and the frequency resource towhich the second channel is allocated is +B in the first slot. Usingthis method makes it possible to obtain effects similar to the effectsdescribed in [inter-slot hopping pattern #1] also for a signal sequencewhere signals having a plurality of different characteristics(stochastic signal, deterministic signal or the like) coexist within aslot (subframe) in addition to stochastic signals.

Embodiment 2

A case has been described in Embodiment 1 where when the frequencyinterval between the first channel and second channel allocated to thefirst slot is B within the IDFT or IFFT band, frequency divisionmultiplexing transmission is performed based on the resource allocationrule whereby the second channel is cyclically allocated to a frequencyresource located B apart from the first channel in the second slotwithin the IDFT or IFFT band (system band) width. The present embodimentwill describe a method of setting frequency interval (frequencydifference) B between a plurality of channels subjected to frequencydivision multiplexing transmission according to the resource allocationrule. For frequency interval B in the second slot, the same value asfrequency interval B in the first slot is maintained as described inEmbodiment 1.

[Frequency Interval Setting Method #1-0]

Of the first channel or second channel frequency-division-multiplexedand transmitted in the first slot or second slot, as frequency resourcesof at least one channel approach both edges of the system band (or moveapart from the central frequency), frequency interval B between thefirst channel and second channel (or maximum value of frequency intervalB) is set to be narrower.

FIG. 25 shows an example of [frequency interval setting method #1-0]. Asshown in FIG. 25, [frequency interval setting method #1-0] controlsfrequency interval B between the frequency resources to which the firstchannel is allocated in the first slot and frequency resources to whichthe second channel is allocated based on the frequency distance fromboth edges of the system band or frequency distance from the centralfrequency. To be more specific, as the frequency distance from bothedges of the system band increases or the frequency distance from thecentral frequency decreases, frequency interval (maximum value offrequency interval) B between the first channel and second channel isset to be narrower.

Generally, when a plurality of channels arefrequency-division-multiplexed and simultaneously transmitted, due tothe influence of non-linearity of the amplifier, inter-modulationdistortion occurs among a plurality of channels, which is liable tocause a problem that leakage to outside the transmission band occurs.However, by using [frequency interval setting method #1-0], frequencyinterval B between the first channel and second channel which arefrequency-division-multiplexed is set to be narrower at both edges ofthe system band where the influence of inter-modulation distortion tooutside the band (where the influence of out-of-band leakage powerincreases) and it is thereby possible to reduce the influence. On theother hand, in the vicinity of the center of the system band where theinfluence of out-of-band leakage power is small, frequency interval Bbetween the first channel and second channel which arefrequency-division-multiplexed is set to be wider (or limitless), and itis thereby possible to maintain the scheduling effect accompanyingflexible resource allocation in the frequency domain. That is, it ispossible to further obtain the above-described effect while maintainingthe effect of Embodiment 1.

[Frequency Interval Setting Method #1-1]

Of the first channel and second channel which arefrequency-division-multiplexed and transmitted, as the frequencydistance between frequency resources of at least one channel and bothedges of the system band decreases, frequency interval B between thefirst channel and second channel (maximum value of the frequencyinterval) is set to be narrower (set to threshold X [RE: ResourceElement] or below). Alternatively, of the first channel and secondchannel which are frequency-division-multiplexed and transmitted,frequency interval B between the first channel and second channel(maximum value of the frequency interval) is set to be narrower as thefrequency distance between frequency resources of at least one channeland the central frequency of the system band increases (set to thresholdX [RE] or below).

FIG. 26 shows a table of correspondence between the frequency distancefrom both edges of the system band and the central frequency of thesystem band, frequency interval B and maximum value (threshold) offrequency interval B based on [frequency interval setting method #1-1].In the example shown in FIG. 26, of the first channel and second channelwhich are frequency-division-multiplexed and transmitted, when thefrequency distance between frequency resources of at least one channeland both edges of the system band is large, no limit is placed on themaximum value of frequency interval B between the first channel andsecond channel. Of the first channel and second channel which arefrequency-division-multiplexed and transmitted, when the frequencydistance between frequency resources of at least one channel and bothedges of the system band is small, the maximum value of frequencydifference B between the two channels is limited to X [RE] or below.

This limits frequency interval B between the first channel and secondchannel which are frequency-division-multiplexed and transmitted to X[RE] or below in the vicinity of both edges of the system band where theinfluence of out-of-band leakage power due to inter-modulationdistortion caused by non-linearity of the amplifier is large, and canlimit the expanse of out-of-band leakage power to a predetermined valueor below.

[Frequency Interval Setting Method #1-2]

When frequency resources of at least one channel of the first channeland second channel which are frequency-division-multiplexed andtransmitted fall within frequency distance Y [RE] from both edges of thesystem band, frequency interval B (maximum value of the frequencyinterval) is set to X [RE] or below.

FIG. 27 shows an example of [frequency interval setting method #1-2]. InFIG. 27, Case (a) shows an example of case where frequency resources ofat least one channel of the first channel and second channel which arefrequency-division-multiplexed and transmitted fall within frequencydistance Y [RE] from both edges of the system band. Furthermore, in FIG.27, Case (b) shows an example of case where frequency resources of atleast one channel of the first channel and second channel which arefrequency-division-multiplexed and transmitted do not fall withinfrequency distance Y [RE] from both edges of the system band.

As shown in FIG. 27, when frequency resources of at least one channel ofthe first channel and second channel which arefrequency-division-multiplexed and transmitted fall within frequencydistance Y [RE] from both edges of the system band, [frequency intervalsetting method #1-2] limits frequency interval B between the firstchannel and second channel to X [RE] or below. On the other hand, whenfrequency resources of at least one channel of the first channel andsecond channel which are frequency-division-multiplexed and transmitteddo not fall within frequency distance Y [RE] from both edges of thesystem band, [frequency interval setting method #1-2] places no limit onfrequency interval B between the first channel and second channel.

FIG. 28 shows a table of correspondence between the frequency distance Y[RE] from both edges of the system band, frequency interval B (maximumvalue of frequency interval B) based on [frequency interval settingmethod #1-2].

This limits frequency interval B between the first channel and secondchannel which are frequency-division-multiplexed and transmitted to X[RE] or below when the frequency distance from both edges of the systemband is in the vicinity of Y [RE] where the influence of out-of-bandleakage power due to inter-modulation distortion caused by non-linearityof the amplifier is large, and can thereby limit the expanse ofout-of-band leakage power to a predetermined value or below. On theother hand, in the band in which the frequency distance from both edgesof the system band where the influence of out-of-band leakage power islarge is other than Y [RE], no limit is placed on frequency interval Bbetween the first channel and second channel which arefrequency-division-multiplexed and transmitted, and it is therebypossible to maintain the scheduling effect accompanying flexibleresource allocation in the frequency domain.

[Frequency Interval Setting Method #1-3]

When frequency resources of at least one channel of the first channeland second channel which are frequency-division-multiplexed andtransmitted fall within a frequency distance of Y [RE] from both edgesof the system band and the (maximum value of) total transmission powerof a frequency-division-multiplexed signal is greater than apredetermined power value (Z [Watt (dBm)]), frequency interval B betweenthe first channel and second channel (maximum value of frequencyinterval B) is set to X [RE] or below.

FIG. 29 shows an example of [frequency interval setting method #1-3].FIG. 29 shows an example of case where transmission powers of the firstchannel and second channel which are frequency-division-multiplexed andtransmitted are the same and Cases (a) to (d) are examples of casesshown below.

Case (a): Example where frequency resources of at least one channel ofthe first channel and second channel which arefrequency-division-multiplexed and transmitted are located withinfrequency distance Y [RE] from both edges of the system band and thetotal transmission power of the frequency-division-multiplexed signal isbelow Z₀ [dBm]

Case (b): Example where frequency resources of at least one channel ofthe first channel and second channel which arefrequency-division-multiplexed and transmitted are located withinfrequency distance Y [RE] from both edges of the system band and thetotal transmission power of the frequency-division-multiplexed signal isequal to or above Z₀[dBm]

Case (c): Example where frequency resources of at least one channel ofthe first channel and second channel which arefrequency-division-multiplexed and transmitted are located outsidefrequency distance Y [RE] from both edges of the system band and thetotal transmission power of the frequency-division-multiplexed signal isequal to or above Z₁[dBm] and equal to or below Z₂[dBm]

Case (d): Example where frequency resources of at least one channel ofthe first channel and second channel which arefrequency-division-multiplexed and transmitted are located outsidefrequency distance Y [RE] from both edges of the system band and thetotal transmission power of the frequency-division-multiplexed signal isequal to or above Z₂[dBm].

FIG. 30 shows a table of correspondence between the frequency distancefrom both edges of the system band, total transmission power of afrequency-division-multiplexed signal, frequency interval B (maximumvalue of frequency interval B) based on [frequency interval settingmethod #1-3] shown in Cases (a) to (d) of FIG. 29.

Based on the table of correspondence shown in FIG. 30, frequencyinterval B between the first channel and second channel (maximum valueof the frequency interval) is set to be limitless in Case (a), X₀[RE] orbelow in Case (b), limitless in Case (c) and X₁[RE] or below in Case(d). Here, there is a relationship of Z₁<Z₂, X₀<X₁.

The greater the frequency interval (frequency difference) between thechannels, the greater is the expanse of inter-modulation distortion of afrequency-division-multiplexed signal caused by non-linearity of theamplifier. In addition, the magnitude of inter-modulation distortion ofthe frequency-division-multiplexed signal is proportional to the cube ofan amplitude product of the frequency-division-multiplexed signal.Therefore, when frequency resources of at least one channel of theplurality of channels which are frequency-division-multiplexed andtransmitted are located at both edges of the system band where theinfluence of out-of-band leakage power is large and the totaltransmission power of the frequency-division-multiplexed signal islarge, the frequency interval (maximum value of the frequency interval)between the plurality of channels which arefrequency-division-multiplexed and transmitted is limited to a certainvalue (X₀[RE]) or below.

Furthermore, even when frequency resources of at least one channel ofthe plurality of channels which are frequency-division-multiplexed andtransmitted are not located within frequency distance Y [RE] from bothedges of the system band, if the total transmission power of thefrequency-division-multiplexed signal is equal to or above a certainspecified value (Z₂ [dBm]), the frequency interval (maximum value of thefrequency interval) between the plurality of channels which arefrequency-division-multiplexed and transmitted is similarly limited to acertain value (X₁ [RE]) or below to reduce the influence ofinter-modulation distortion inside and outside the system band.

Thus, by setting the frequency interval of thefrequency-division-multiplexed signal by taking into account theinfluence of the magnitude of transmission power of thefrequency-division-multiplexed signal in addition to the positions offrequency resources in which the plurality of channelsfrequency-division-multiplexed and transmitted are arranged, it ispossible to control the influence of interference of inter-modulationdistortion on other channels with higher accuracy than when [frequencyinterval setting method #1-2] is used in addition to the above effect.

Frequency interval B may also be set based on transmission power of atleast one channel of the plurality of channels making up thefrequency-division-multiplexed signal instead of the total transmissionpower of the frequency-division-multiplexed signal. FIG. 31 shows atable of correspondence between the frequency distance from both edgesof the system band, transmission power of one channel of a plurality ofchannels making up a frequency-division-multiplexed signal, frequencyinterval B (maximum value of frequency interval B). Effects similar tothose described above can be obtained even when frequency interval B isset based on the transmission power of at least one channel of theplurality of channels making up the frequency-division-multiplexedsignal instead of the total transmission power of thefrequency-division-multiplexed signal. However, frequency interval B ispreferably set based on the transmission power value of a channel havinghigh transmission power as at least one channel. This makes it possibleto control the influence of interference of inter-modulation distortionon other channels more accurately than when based on the transmissionpower value of a channel having smaller transmission power.

Furthermore, frequency interval B may also be set based on an amplitudeproduct of each channel or power product (or power of a power product)making up the frequency-division-multiplexed signal instead of the totaltransmission power of the frequency-division-multiplexed signal. It ispossible to obtain effects similar to those described above in thiscase, too.

Furthermore, when the first channel and second channel making up thefrequency-division-multiplexed signal are PUSCH and PUCCH, the frequencydistance may be calculated based on frequency resources in which PUSCHis arranged. As described above, PUCCH hops at both edges of the systemband between slots. On the contrary, PUSCH hops in frequency bandssandwiched between the hopping regions of PUCCH. That is, PUCCH isalways arranged on a frequency located farther (closer to both edges ofthe system band) from the central frequency than PUSCH. Therefore, as aresult of calculating the frequency distance from both edges or thecentral frequency of the system band based on frequency resources onwhich PUSCH is arranged, if the frequency distance between frequencyresources on which PUSCH is arranged and both edges or the centralfrequency of the system band is Y [RE] or below, it is clear that thefrequency distance from frequency resources on which PUCCH is arrangednecessarily becomes Y [RE] or below. That is, calculation of thefrequency distance between the frequency resources of PUCCH and bothedges or the central frequency of the system band can be omitted.

Embodiment 3

The present embodiment reuses the method in LTE Re1.8 that appliesfrequency hopping to PUCCH and PUSCH independently of each otheraccording to the resource allocation rule for frequency divisionmultiplexing and transmitting PUSCH and PUCCH. Furthermore, the presentembodiment generates a coordinated frequency hopping pair of PUSCH andPUCCH according to the number of subbands included in the system bandand resource numbers of frequency resources on which PUCCH is arrangedin the first slot.

The number of subbands is set by the base station. The base station setsthe number of subbands so that the bandwidth of subbands obtained bydividing the band of the system band to which frequency hopping isapplied is, for example, a natural number multiple of an RBG (ResourceBlock Group) size. Information of the number of subbands set by the basestation is included, for example, in frequency hopping indicationinformation (or signaling information of a higher layer (RRC (RadioResource Control)) and reported to the terminal.

Furthermore, there is a correlation as shown in FIG. 32 between resourcenumber m of a frequency resource on which PUCCH is arranged and theposition of a physical channel resource (see Non-Patent Literature 3).That is, as shown in FIG. 32, in the first slot, a frequency resourcewhose resource number m is an even number is associated with a physicalchannel resource in the lower part of the system band (that is, lowfrequency side) and a frequency resource whose resource number m is anodd number is associated with a physical channel resource in the upperpart of the system band (that is, high frequency side). On the otherhand, in the second slot, a frequency resource whose resource number mis an even number is associated with a physical channel resource in theupper part of the system band (that is, high frequency side) and afrequency resource whose resource number m is an odd number isassociated with a physical channel resource in the lower part of thesystem band (that is, low frequency side).

In the present embodiment, PUSCH and PUCCH are caused to performfrequency hopping according to the number of subbands included in thesystem band and resource number m of each frequency resource on whichPUCCH is arranged in the first slot using the correspondence betweenresource number m and a physical channel resource in each slot.

[Inter-Slot Hopping Oattern #9] (Number of Subbands=1)

FIG. 33 and FIG. 34 show an example of [inter-slot hopping pattern #9].[Inter-slot hopping pattern #9] is an inter-slot hopping pattern whenonly one subband is included in the system band (when the number ofsubbands=1). In [inter-slot hopping pattern #9], PUSCH (second channel)is arranged in the first slot and second slot as follows.

(a) When PUCCH (first channel) is arranged on a frequency resource whoseresource number m is an even number in the first slot, PUSCH (secondchannel) is arranged on a frequency resource in a lower band within thesubband in the first slot and PUSCH (second channel) is arranged on afrequency resource in an upper band within the subband in the secondslot (see FIG. 33).

(b) When PUCCH (first channel) is arranged on a frequency resource whoseresource number m is an odd number in the first slot, PUSCH (secondchannel) is arranged on a frequency resource in an upper band within thesubband in the first slot and PUSCH (second channel) is arranged on afrequency resource in a lower band within the subband in the second slot(see FIG. 34).

That is, in one of the above cases in (a) and (b), PUSCH (secondchannel) is arranged in the first slot and second slot using mirroringwithin the subband. Here, “mirroring” refers to an operation of shiftinga resource in question to a frequency resource position mirror symmetricwith respect to the central frequency within the subband (frequencyresource positions whose frequency distances from the central frequencywithin the subband are the same).

This makes it possible to reduce the influence of out-of-band leakagepower while reusing the method used in LTE Re1..8 of causing PUCCH andPUSCH to perform frequency hopping independently of each other, that is,while maintaining backward compatibility with LTE Re1.8.

Points to enable out-of-band leakage power to be reduced will beadditionally described. The following description will be given takingabove-described case in (a) as an example. As a comparison target in(a), suppose a case where when PUCCH is arranged on a frequency resourcewhose resource number m is an even number in the first slot, PUSCH isarranged on a frequency resource in an “upper” band within the subbandin the first slot and arranged on a frequency resource in a “lower” bandwithin the subband in the second slot. FIG. 35 is an arrangement examplein the comparison target and PUSCH (second channel) is arranged in thesecond slot using mirroring within the subband.

When PUCCH is arranged on a frequency resource whose resource number mis an even number in the first slot, the frequency interval betweenPUSCH and PUCCH is smaller in the case where PUSCH is arranged on afrequency resource in a “lower” band than in the case where PUSCH isarranged on a frequency resource in an “upper” band within the subbandin the first slot. On the other hand, when PUCCH is arranged on afrequency resource whose resource number m is an even number in thesecond slot, the frequency interval between PUSCH and PUCCH is smallerin the case where PUSCH is arranged on a frequency resource in an“upper” band than in the case where PUSCH is arranged on a frequencyresource in a “lower” band within the subband in the second slot.

Therefore, in both the first slot and the second slot, the frequencyinterval can be maintained to be always smaller in (a) than the abovecomparison target (see FIG. 33 and FIG. 35). As the frequency intervalof each channel making up a frequency-division-multiplexed signalbecomes smaller, the expanse of inter-modulation distortion can bereduced, and therefore the influence of out-of-band leakage power can bereduced in (a) compared to the comparison target. The same applies tothe case in (b).

[Inter-Slot Hopping Pattern #10] (Number of Subbands>1)

FIG. 36 and FIG. 37 show an example of [inter-slot hopping pattern #10].[Inter-slot hopping pattern #10] is an inter-slot hopping pattern whenthe number of subbands>1. FIG. 36 and FIG. 37 show examples when thenumber of subbands=3. In [inter-slot hopping pattern #10], PUSCH (secondchannel) is arranged in the first slot and second slot as follows.

(a) When PUCCH is arranged on a frequency resource whose resource numberm is an even number in the first slot,

PUSCH is arranged on a frequency resource in a “lower (that is, lowfrequency side)” band in each subband in the first slot and arranged ona frequency resource in an “upper (that is, high frequency side)” bandin each subband in the second slot (see FIG. 36).

(b) When PUCCH is arranged on a frequency resource whose resource numberm is an odd number in the first slot, PUSCH is arranged on a frequencyresource in an “upper (that is, high frequency side)”band within eachsubband in the first slot and arranged on a frequency resource in a“lower (that is, low frequency side)” band within each subband in thesecond slot (see FIG. 37).

That is, in one of above cases (a) and (b), PUSCH (second channel) isarranged in the first slot and second slot using mirroring within thesubband.

Thus, in the case where the number of subbands>1, it is also possible toreduce the influence of out-of-band leakage power as in the case of[inter-slot hopping pattern #9] while reusing the method used in LTERe1.8 of causing PUCCH and PUSCH to perform frequency hoppingindependently of each other, that is, while maintaining backwardcompatibility with LTE Re1.8.

Thus, according to the resource allocation rule in the presentembodiment, PUSCH is arranged in the first slot according to resourcenumber m of PUCCH in the first slot using a correlation between resourcenumber m of a frequency resource on which PUCCH is arranged and theposition of a physical channel resource. Furthermore, PUSCH is arrangedin the second slot using mirroring within the subband as in the case ofLTE Re1.8. This makes it possible to maintain the frequency intervalbetween the first channel and second channel between the first slot andsecond slot while maintaining backward compatibility with LTE Re1.8, andcan thereby reduce the influence of out-of-band leakage power.

Embodiment 4

A case has been described in Embodiment 3 where according to theresource allocation rule for frequency division multiplexing andtransmitting PUSCH and PUCCH, inter-slot frequency hopping of PUSCH isperformed using mirroring while maintaining the frequency intervalbetween the first channel and second channel between slots. The presentembodiment will describe a case where inter-slot frequency hopping ofPUSCH is performed using a cyclic frequency shift instead of mirroring.In the resource allocation rule for frequency division multiplexing andtransmitting PUSCH and PUCCH, the present embodiment will also reuse themethod of performing frequency hopping LTE Re1.8 for PUCCH and PUSCHindependently of each other as in the case of Embodiment 3.

In LTE Re1.8, PUSCH is made to cyclic frequency shift (wrap-around)within a hopping band (<=system band) and thereby perform inter-slotfrequency hopping. On the other hand, PUCCH is made to hop frequencyresources associated with resource number m (0, 1, 2, . . . ) defined atboth edges of the system band between slots. This results in a problemthat it is difficult to simply introduce coordinated frequency hoppingfor maintaining the frequency interval between a plurality of channels(e.g. PUSCH and PUCCH) to the Re1.8 scheme, which is the feature of thepresent invention described in Embodiment 1.

Thus, the present embodiment corrects (modifies) the frequency hoppingmethod based on a PUSCH cyclic frequency shift of Re1.8 to address theabove-described problem while reusing the frequency hopping method ofRe1.8. The present embodiment corrects the amount of cyclic frequencyshift of Re1.8 when causing PUSCH to wrap-around (cyclic frequencyshift) within the system bandwidth.

To be more specific, a correction term of (system band−hopping band) isintroduced and the amount of cyclic frequency shift of PUSCH is definedas equation 5.

(Equation 5)

Amount of cyclic frequency shift of PUSCH=(amount of cyclic frequencyshift of Re1.8+(system band−hopping band))mod(system band)   [5]

where, “mod” represents a modulo operation.

Furthermore, when causing PUSCH to wrap-around within the hoppingbandwidth, the present embodiment defines the amount of cyclic frequencyshift of PUSCH as equation 6.

(Equation 6)

Amount of cyclic frequency shift of PUSCH=(hopping band−(PUSCHbandwidth+frequency difference (+B)))mod(hopping band)   [6]

FIG. 38 shows a correction term and an amount of cyclic frequency shiftwithin a hopping band when causing PUSCH to wrap-around (cyclicfrequency shift) within the system bandwidth according to the presentembodiment.

Thus, according to the resource allocation rule of the presentembodiment, a cyclic frequency shift is corrected based on the hoppingband in which PUSCH performs frequency hopping. This allows effectssimilar to those of Embodiment 1 to be obtained by introducing acorrection term to the frequency hopping method used in Re1.8 and onlyapplying minor modifications.

Embodiment 5

The present embodiment will describe a case where the resourceallocation rule described in the above embodiment is generalized to acase where the number of channels which arefrequency-division-multiplexed and transmitted is n.

[Inter-Slot Hopping Pattern #11]

FIG. 39 shows an example of [inter-slot hopping pattern #11]. FIG. 39shows a case where three channels are frequency-division-multiplexed andtransmitted. In FIG. 39, a first channel, second channel and thirdchannel are arranged in the first slot in order starting from thecomponent of the lowest frequency. Furthermore, the respective frequencyintervals are B₀ and B₁. Furthermore, the frequency bandwidth of thefirst channel is the same as that of the second channel.

When three channels are frequency-division-multiplexed and transmitted,FIG. 39 shows candidates of mapping positions of the respective channelsin the second slot after frequency hopping. The first channel and secondchannel having the same frequency bandwidth need only to be mapped atfrequency resource positions spaced by frequency interval B₀ and theorder of the respective channels has no preference. That is, there is afeature that the order of channels having the same frequency bandwidthin the frequency domain can be changed as long as frequency interval B₀between the first channel and second channel is maintained.

Furthermore, a plurality of channels may be cyclically shifted in theIFFT frequency band as long as frequency intervals B₀ and B₁ (relativefrequency positional relationship between channels and order inbandwidth size in the frequency domain) are maintained. This allows thefrequency interval of each channel to be maintained between the firstslot and second slot and enables effects similar to those of the aboveembodiments to be obtained.

[Inter-Slot Hopping Pattern #12]

FIG. 40 shows an example of [inter-slot hopping pattern #12]. FIG. 40 isan example of case where three channels arefrequency-division-multiplexed and transmitted as in the case of FIG.39. The difference in the resource allocation rule based on the patternshown in FIG. 40 and FIG. 39 is that in [inter-slot hopping pattern#12], the first channel and second channel in the second slot areassumed to be one channel group (block) and two candidates are providedas mapping position candidates of the third channel. That is, a mappingposition candidate of the third channel is secured in a frequencyresource located frequency difference +B₁ or frequency difference −B₁apart from one channel group (block) comprised of the first channel andsecond channel in the second slot. This makes it possible to maintainthe frequency interval between one channel group (block) of the firstchannel and second channel and the third channel in the first slot andsecond slot and obtain effects similar to those in the aboveembodiments.

[Inter-Slot Hopping Pattern #13]

FIG. 41 shows an example of [inter-slot hopping pattern #13]. FIG. 41 isan example of case where n channels are frequency-division-multiplexedand transmitted. In FIG. 41, n channels are arranged in order of firstchannel, second channel, . . . , n-th channel in the first slot startingfrom the component of the lowest frequency. In [inter-slot hoppingpattern #13], a mapping position candidate of the n-th channel isdetermined from a channel group (block) comprised of first, . . . , to(n−1)-th channels in the second slot after frequency hopping. To be morespecific, a mapping position candidate of the n-th channel is secured ina frequency resource located frequency difference +B_(n−1) or frequencydifference −B_(n−1) apart from one channel group (block) comprised offirst to (n−1)-th channels in the second slot.

FIG. 42 is a flowchart for realizing inter-slot frequency hopping basedon [inter-slot hopping pattern #13].

(1) Two channels (first and second channels) are selected from among nchannels and the first channel is set as a reference channel.

(2-1) The reference channel is cyclically frequency shifted and causedto perform inter-slot frequency hopping.

(2-2) The second channel is mapped at the frequency position byfrequency difference +B₁ or −B₁ between the reference channel and thesecond channel apart from the reference channel.

(3-1) One channel is newly selected from among n channels as an i-thchannel (i>=2).

(3-2) Assuming all channels after frequency hopping as one channel group(block), the channel group (block) is set as one new reference channel.

(3-3) An i-th channel is mapped at a frequency position by frequencydifference +B_(i) or −B_(i) between the new reference channel and thei-th channel apart from the new reference channel.

Hereinafter, (3-1) to (3-3) will be repeated.

Thus, according to the resource allocation rule of the presentembodiment, when a frequency division multiplexing transmission signalis comprised of n (integer of n>2) channels, the frequency intervalbetween channels is also maintained between slots. This makes itpossible to perform inter-slot frequency hopping without changing theinstantaneous power distribution characteristic of a transmission signalbetween two slots.

Embodiment 6

A feature of the present embodiment is that frequency differences amonga plurality of channels are maintained within the respective componentbands and relative interval Δ between the component bands is changedbetween slots using a plurality of channels within a plurality ofsimultaneously transmitted component bands as a block.

As a feature of inter-modulation distortion generated when a pluralityof channels are simultaneously transmitted, frequency positions whereinter-modulation distortion occurs depend on a frequency differencebetween simultaneously transmitted channels. That is, when thedifference between two channel frequencies is B, inter-modulationdistortion occurs at a frequency position at a frequency distancecorresponding to a multiple of B from a frequency position of onechannel of a plurality of simultaneously transmitted channels.

[Inter-Slot Hopping Pattern #14]

Taking advantage of the above-described features, a switchover is madebetween following two frequency hopping patterns 1 and 2 to be usedbetween component bands (CC). For example, during intra-band continuouscarrier aggregation, a switchover is made between frequency hoppingpatterns for each component band.

Hopping pattern 1: When the frequency difference is +(−)B in the firstslot, suppose the frequency difference is +(−)B in the second slot.

Hopping pattern 2: When the frequency difference is +(−)B in the firstslot, suppose the frequency difference is −(+)B in the second slot.

This causes inter-modulation distortion whose order differs from oneslot to another to be received, and can thereby randomize interferencedue to inter-modulation distortion that occurs between differentcomponent bands.

FIG. 43 shows an example of [inter-slot hopping pattern #14]. FIG. 43shows an example of case where four channels are simultaneouslytransmitted using two component bands (#0, #1) (two channels aretransmitted in each component band).

In the first slot before frequency hopping, the frequency differencebetween two channels (first channel and second channel) in componentband #0 is +B₀ and the frequency difference between two channels (firstchannel and second channel) in component band #1 is +B₁. Furthermore, arelative frequency interval between the two channels of component band#0 and the two channels of component band #1 is Δ₀. In this case, theinter-modulation distortion of component band #0 (#1) matches thefrequency position of at least one channel of the simultaneouslytransmitted channels of component band #1 (#0). For example, frequencypositions f₁ and f₁+2B₀ correspond to that case. That is, a case isindicated where both component bands receive interference caused byinter-modulation distortion from different component bands.

In the second slot after the frequency hopping, the frequency differencebetween the two channels of component band #0 is −B₀ and the frequencydifference between the two channels of component band #1 is +B₁.Furthermore, a relative frequency interval between the two channels ofcomponent band #0 and the two channels of component band #1 is Δ₁ (≠Δ₀).In this case, since Δ₁≠Δ₀, the plurality of respective simultaneouslytransmitted channels of component band #0 and component band #1 receivedifferent (order) inter-modulation distortion (from different componentbands) from that of the case with the first slot. That is, it ispossible to realize randomization of interference due tointer-modulation distortion simultaneously transmitted between the firstslot and second slot.

A case has been described in the above embodiments where the frequencydifference between the first channel and second channel of componentband #0 and the frequency difference between the first channel andsecond channel of component band #1 have a relationship of B₀≠B₁, butthe frequency differences may be set to the same value (B₀=B₁).

As one method of maintaining the frequency difference between aplurality of channels within each component band and changing relativeinterval Δ between component bands by assuming a plurality ofsimultaneously transmitted component bands as a block in theabove-described embodiments, the amounts of cyclic frequency shift ofthe plurality of channels within each component band may be set to thesame value and set to different values between the component bands.

In the above-described embodiments, the above-described embodiment maybe applied to only a case where at least one channel exists in thefrequency bands at both edges Y [RE] of each component band. This causesinter-modulation distortion of different orders to be received at bothedges of the system between the slots, which allows randomization ofinterference. Furthermore, in the vicinity of the central part of thesystem band where the influence of inter-modulation distortion is small,it is possible to keep a scheduling effect accompanying flexiblefrequency allocation.

Embodiment 7

A feature of the present embodiment is that a first channel and secondchannel after frequency hopping are mapped, in a second slot after thefrequency hopping, to frequency resources other than a multiple ofabsolute value B of a frequency difference in a first slot.

As in the case of Embodiment 6, as a feature of inter-modulationdistortion which occurs when a plurality of channels are simultaneouslytransmitted, the present embodiment takes advantage of the fact that thefrequency position where inter-modulation distortion occurs depends onthe frequency difference between simultaneously transmitted channels.

This makes it possible to change an interfered terminal

(UE) due to inter-modulation distortion between slots (it is possible toreduce the probability of receiving large inter-modulation distortioninterference from a specific terminal (UE) for two consecutive slots asviewed from the interfered terminal (UE)).

[Inter-Slot Hopping Pattern #15]

FIG. 44 shows an example of [inter-slot hopping pattern #15] (case withtwo terminals (UE)). FIG. 44 shows a case where in the first slot(before inter-slot frequency hopping), UE #0 simultaneously transmits afirst channel (frequency position: f₀) and second channel (frequencyposition: f₁) with frequency interval B₀ and UE #1 transmits one channelallocated to frequency position f₀+2B₀. Therefore, fifth order and thirdorder inter-modulation distortion components of UE #0 are generated atfrequency positions of f₀−2B₀ (f₁+2B₀) and f₀−B₀ (f₁+B₀) respectively.That is, in the first slot, UE #0 gives UE #1 interference due tointer-modulation distortion at frequency position f₀+2B₀.

In the second slot (after inter-slot frequency hopping), UE #0simultaneously transmits two channels from any positions other thanfrequency positions of a plurality of channels simultaneouslytransmitted of UE #0 in the first slot and from any positions other thana frequency position at a frequency distance corresponding to a multipleof frequency interval B₀ from the frequency position of one channel ofthe plurality of channels in the first slot, while maintaining frequencyinterval B₀ between the first channel and second channel. In FIG. 44,the signal of UE #0 is transmitted by being mapped to a band at otherthan frequency resource positions of f₀−2B₀, f₀−B₀, f₀, f₁, f₁+B₀ andf₁+2B₀ in the second slot.

This makes it possible to change an interfered UE due to inter-slotinter-modulation distortion (it is possible to reduce the probability ofreceiving large inter-modulation distortion interference from a specificUE for two consecutive slots as seen from the interfered UE). Theabove-described embodiment may be applicable to one of a channel havinga bandwidth of linear spectrum and a channel having a certain band.

Although the above-described embodiments have not referred to frequencyresource allocation units of PUCCH and PUSCH which are (first, second, .. . ) channels that transmit a control signal and data signal, frequencyresources may be allocated in a unit called “resource block (RB)” makingup one allocation unit to perform inter-slot frequency hopping bybundling a plurality of resource elements (RE: Resource Elements,subcarriers, tones) as an allocation unit. Furthermore, by bundling aplurality of REs, frequency resources may be allocated in a unit called“resources block group (RBG)” making up one allocation unit to performinter-slot frequency hopping. Furthermore, one resource element(subcarrier, tone, bin) may be configured as an allocation unit andfrequency resources may be allocated to perform inter-slot frequencyhopping.

Although all the above-described embodiments have described onlyinter-slot frequency hopping between slots in a subframe, when frequencyhopping is performed between subframes, frequency hopping patterns(frequency difference B between a plurality of channels betweensubframes, amount of cyclic frequency shift between a plurality ofchannel slots and cyclic frequency shift direction) may differ betweenthe subframes irrespective of whether or not inter-slot frequencyhopping is applied.

Furthermore, a case has been described in all the above-describedembodiments where signals spread in a DFT matrix and CAZAC sequence arefrequency-division-multiplexed, but the present invention is alsoapplicable to a configuration in which unspread signals arefrequency-division-multiplexed, for example, frequency divisionmultiplexing transmission in OFDM transmission. By applying the presentinvention to OFDM transmission, it is possible to suppress inter-slotchanges in instantaneous power distribution characteristic (e.g. CCDFcharacteristic of PAPR) of a time waveform of an OFDM transmissionsignal.

Furthermore, a case has been described in all the above-describedembodiments where frequency hopping is performed between slots, but thetime unit for performing frequency hopping may have a length other thanthe slot length (time unit longer than the slot length ((sub)framelength or the like), shorter time unit (1 SC-FDMA symbol length)). Forexample, a plurality of channels may be caused to perform frequencyhopping based on the above-described method within a sub frame orbetween subframes (intra-subframe and inter-subframe frequency hopping).This makes it possible to obtain effects similar to those describedabove for periods during which a frequency difference between aplurality of channels is maintained in frequency hopping in that timeunit.

Furthermore, a case has been described in all the above-describedembodiments where a plurality of channels are mapped to discontinuousfrequency resources, but a plurality of channel may also be mapped tocontinuous frequency resources. That is, a case with frequencydifference B=1 subcarrier (resource element) interval is equivalent to acase where a plurality of different channels are mapped to continuousneighboring frequency resources (block). Inter-slot frequency hoppingmay be performed, for example, as shown in FIG. 24, by mapping PUCCH 1of the first channel and PUCCH 2 of the second channel to neighboringfrequency resources in the PUCCH region in the first-half slot andcyclically frequency shifting PUCCH 1 and PUCCH 2 within the IFFTbandwidth while maintaining a frequency difference B=1 subcarrier(resource element) interval between PUCCH 1 and PUCCH 2.

In all the above-described embodiments, in a case where for a timeperiod during which a plurality of channels making up frequency divisionmultiplexing transmission are transmitted, if the channels aretransmitted in a predetermined transmission format, a certain modulationscheme (e.g. QPSK, QAM modulation) or (and) a certain transmission power(density) value may be maintained for the time period.

In all the above-described embodiments, as a method of maintaining afrequency difference between the plurality of channels making upfrequency division multiplexing transmission, there may be a case wherea frequency hopping pattern of each channel is determined based on acertain sequence such as a PN sequence and random sequence or a casewhere parameters for generating the sequence are determined by a cellID, frame number, subframe number or the like. In such cases, in orderthat a plurality of channels may have the same sequence, the samehopping sequence corresponding to the respective channels or (and) thesame parameter for generating the sequence may be set.

A case has been described in all the above-described embodiments where afrequency-division-multiplexed signal is transmitted from onetransmitting antenna, but in a case where MIMO (Multi-InputMulti-Output) transmission with a plurality of antennas is performed,each frequency-division-multiplexed channel may be multiplied by anidentical (time-invariant) linear spatial precoding matrix for a timeperiod spanning over two slots. That is, the same matrix may be used forthe precoding matrix by which each channel is multiplied in the firstslot before frequency hopping and the precoding matrix by which eachchannel is multiplied in the second slot after frequency hopping. Thismakes it possible to obtain effects similar to those described above.

Furthermore, a case has been described in all the above-describedembodiments where a CAZAC sequence or DFT sequence is used to spreadPUCCH or PUSCH as the spreading method, but the spreading method is notlimited to such sequences. For example, other sequences such asWalsh-Hadamard sequence, Gold sequence, PN sequence may also be used forspreading. This also makes it possible to obtain effects similar tothose described above.

Furthermore, a case has been described in all the above-describedembodiments where Acknowledgment (ACK), Non-Acknowledgment (NACK),Scheduling Request (SR), Channel Quality Indicator (CQI), Channel StateInformation (CSI) or the like is individually mapped as controlinformation to be mapped to PUCCH, but the present invention is notlimited to this. The present invention is also applicable to aconfiguration in which at least two pieces of control information of ACK(or NACK), SR, CQI, CSI or the like are mapped to one PUCCH resource.This also makes it possible to obtain effects similar to those describedabove.

Furthermore, data information has been described as information to bemapped to PUSCH in all the above-described embodiments, but withoutbeing limited to the configuration, data information and controlinformation (ACK, NACK, SR, CQI, CSI or the like) may be mapped to onePUSCH. This also makes it possible to obtain effects similar to thosedescribed above.

Furthermore, in the above-described embodiments, when a plurality ofPUCCHs in a plurality of component bands are inter-slot frequency hoppedduring carrier aggregation using two or more component bands (CC:component carriers), hopping may be performed with the amount of cyclicshift (CS) of the CAZAC sequence of PUCCH in each component band, whichis spread using a CAZAC sequence, differing from one component band toanother or being fixed to the same value. This makes it possible toobtain effects similar to those described above.

Furthermore, a configuration has been described in the above-describedembodiments in which control information related to inter-slot frequencyhopping ((reserved) resource allocation, amount of cyclic shift offrequency hopping, hopping pattern or the like) is reported via acontrol channel (e.g. PDCCH) of the physical layer, but the presentinvention is not limited to this. For example, the control informationmay also be reported using a reporting method for control information ofa higher layer such as UE common signaling of RRC (Radio ResourceControl) and UE-specific signaling. Furthermore, the control informationmay also be reported with system information (SI) using a broadcastchannel (BCH). This makes it possible to obtain effects similar to thosedescribed above.

Furthermore, a case has been described in the above-describedembodiments where one IDFT (or IFFT) is used, but the present inventionis also applicable to a case with two or more IDFTs (or IFFTs). In thatcase, the frequency interval (frequency difference) between a pluralityof channels may differ within a different IDFT (or each IFFT) band ifinter-slot frequency hopping is performed which maintains the frequencyinterval (frequency difference) between the plurality of channels withineach IDFT (or each IFFT) band. When, for example, inter-slot frequencyhopping is used which maintains frequency difference B₁ between twochannels within IDFT of component band #1, inter-slot frequency hoppingmay also be performed which maintains frequency difference B₂ (B₁)between two channels within IDFT of component band #2.

However, the amount of cyclic frequency shift between two channels inIDFT of component band #1 is preferably the same value as the amount ofcyclic frequency shift between two channels in IDFT of component band#2. Thus, when a plurality of channels are simultaneously transmitted ina plurality of component bands (e.g. when four channels (two channels ineach component band) are simultaneously transmitted in two componentbands), effects similar to those described above can be obtained in thecomponent band as a whole.

The above-described embodiments have been described as an antenna, butthe present invention is equally applicable to an antenna port.

The “antenna port” refers to a logical antenna comprised of one or aplurality of physical antennas. That is, the antenna port does notalways refer to one physical antenna but may refer to an array antennaor the like comprised of a plurality of antennas.

For example, 3GPP LTE does not specify of how many physical antennas anantenna port is composed but specifies the antenna port as a minimumunit whereby a base station can transmit different reference signals.

The antenna port may also be defined as a minimum unit for multiplying aprecoding vector by a weight.

Furthermore, although cases have been described with the embodimentsabove where the present invention is configured by hardware, the presentinvention may be implemented by software.

Each function block employed in the description of the aforementionedembodiments may typically be implemented as an LSI constituted by anintegrated circuit. These may be individual chips or partially ortotally contained on a single chip. “LSI” is adopted here but this mayalso be referred to as “IC,” “system LSI,” “super LSI” or “ultra LSI”depending on differing extents of integration.

Further, the method of circuit integration is not limited to LSI's, andimplementation using dedicated circuitry or general purpose processorsis also possible. After LSI manufacture, utilization of an FPGA (FieldProgrammable Gate Array) or a reconfigurable processor where connectionsand settings of circuit cells within an LSI can be reconfigured is alsopossible.

Further, if integrated circuit technology comes out to replace LSI's asa result of the advancement of semiconductor technology or a derivativeother technology, it is naturally also possible to carry out functionblock integration using this technology. Application of biotechnology isalso possible.

The disclosures of Japanese Patent Application No. 2009-131255, filed onMay 29, 2009, and Japanese Patent Application No. 2010-105329, filed onApr. 30, 2010, including the specifications, drawings and abstracts, areincorporated herein by reference in their entirety.

INDUSTRIAL APPLICABILITY

The radio communication apparatus and frequency hopping method accordingto the present invention are suitable for use in a radio communicationapparatus or the like that frequency-division-multiplexes and transmitsa plurality of channels.

REFERENCE SIGNS LIST

-   100 Base station-   101, 201 Transmitting/receiving antenna port-   102, 202 Radio reception processing section-   103 SC-FDMA signal demodulation section-   104, 204 Demodulation section-   105, 205 Channel decoding section-   106 Quality measuring section-   107 Frequency hopping control section-   108 Scheduling section-   109 Control information generation section-   110-1, 110-2, 208-1, 208-2 Channel coding section-   111-1, 111-2, 209-1, 209-2 Modulation section-   112 OFDM signal modulation section-   113, 215 Radio transmission processing section-   200, 200A terminal-   203 OFDM signal demodulation section-   206 Control information extraction section-   207 Control section-   210 DFT section-   211 Spreading section-   212 Mapping section-   213 IFFT section-   214 CP insertion section-   216 Spectrum division section

1. A radio communication apparatus comprising: an arrangement sectionthat arranges a signal of a first channel to frequency resources of afirst slot and a second slot transmitted in a predetermined transmissionformat and arranges a signal of a second channel to frequency resourceslocated a predetermined frequency interval apart from a frequencyresource of the frequency resources of the first slot in which the firstchannel is arranged; and an inverse Fourier transform section thatapplies an inverse discrete Fourier transform or an inverse fast Fouriertransform to the signals arranged in the first channel and the secondchannel, wherein the arrangement section cyclically frequency shiftswithin an inverse discrete Fourier transform or inverse fast Fouriertransform bandwidth while maintaining the predetermined frequencyinterval, arranges the signals of the first channel and the secondchannel to frequency resources of the second slot and thereby causes thefirst channel and the second channel to perform frequency hoppingbetween the first slot and the second slot.
 2. The radio communicationapparatus according to claim 1, wherein, when a frequency differencefrom the frequency resource to which the first channel is allocated tothe frequency resource to which the second channel is allocated in thefirst slot is +B (−B), the arrangement section cyclically frequencyshifts the second channel to a frequency resource located +B (−B) apartfrom the first channel in the second slot within an inverse discreteFourier transform or inverse fast Fourier transform bandwidth.
 3. Theradio communication apparatus according to claim 1, wherein, when afrequency difference from the frequency resource to which the firstchannel is allocated to the frequency resource to which the secondchannel in the first slot is allocated is +B (−B), the arrangementsection cyclically frequency shifts the second channel to a frequencyresource located −B (+B) apart from the first channel in the second slotwithin an inverse discrete Fourier transform or inverse fast Fouriertransform bandwidth.
 4. The radio communication apparatus according toclaim 1, wherein the predetermined frequency interval is set to be equalto or above a total bandwidth of the first channel region cyclically andcontinuously present in an inverse discrete Fourier transform or inversefast Fourier transform bandwidth.
 5. The radio communication apparatusaccording to claim 1, wherein the predetermined frequency interval isset to be equal to or above a total bandwidth of guard bands (zeropadding) cyclically and continuously present in an inverse discreteFourier transform or inverse fast Fourier transform bandwidth.
 6. Theradio communication apparatus according to claim 1, wherein thepredetermined frequency interval is set to be equal to or above a totalbandwidth of the first channel region and a guard band (zero padding)cyclically and continuously present in an inverse discrete Fouriertransform or inverse fast Fourier transform bandwidth.
 7. The radiocommunication apparatus according to claim 1, wherein a signal mapped inan i-th channel (i=1 or 2) of the second slot is a signal resulting fromrepetition of a signal mapped in an i-th channel of the first slot. 8.The radio communication apparatus according to claim 1, wherein a signalmapped to at least one channel of the first channel and the secondchannel is a signal spread by a discrete Fourier transform or constantamplitude zero autocorrelation sequence.
 9. The radio communicationapparatus according to claim 1, wherein a signal mapped to two or morediscontinuous frequency resources is a signal resulting fromspectrum-dividing a signal spread by a discrete Fourier transform orconstant amplitude zero autocorrelation sequence.
 10. The radiocommunication apparatus according to claim 1, wherein a signal mapped totwo or more discontinuous channels of a plurality of channels frequencyhopped between slots is a signal resulting from spectrum-dividing asignal spread by a discrete Fourier transform or constant amplitude zeroautocorrelation sequence.
 11. The radio communication apparatusaccording to claim 1, wherein the predetermined frequency intervalbecomes narrower as a frequency resource of at least one of the firstchannel or the second channel approaches both edges of the inversediscrete Fourier transform or inverse fast Fourier transform band ormoves apart from a central frequency of the inverse discrete Fouriertransform or inverse fast Fourier transform band.
 12. The radiocommunication apparatus according to claim 1, wherein the amount ofcyclical frequency shift is an amount of shift corrected based on ahopping band in which the first channel or the second channel performsfrequency hopping.
 13. A frequency hopping method comprising: anarranging step of arranging a signal of a first channel to frequencyresources of a first slot and a second slot transmitted in apredetermined transmission format and arranging a signal of a secondchannel in a frequency resource located a predetermined frequencyinterval apart from a frequency resource of the frequency resources ofthe first slot in which the first channel is arranged; and atransforming step of applying an inverse discrete Fourier transform oran inverse fast Fourier transform to the signals arranged in the firstchannel and the second channel, wherein, in the arranging step, thesignals of the first channel and the second channel are cyclicallyfrequency shifted within an inverse discrete Fourier transform orinverse fast Fourier transform bandwidth while maintaining thepredetermined frequency interval, arranged to frequency resources of thesecond slot, and the signals of the first channel and the second channelare thereby caused to perform frequency hopping between the first slotand the second slot.